MP1584EN3A,15MHz的,28V降压型转换器中文
士兰微 400KHz 2A降压型DC-DC转换器 说明书
电感选择
当输出电流较大时，转换器工作在连续电流模式，即电 感电流连续，不会降至 0。电感的取值会影响到电感电流的纹 波，两者之间的关系由下式确定。
L = VO ⋅(VI − VO ) 。 VI ⋅ fS ⋅ ΔI
其中，VI 是输入电压， VO 是输出电压， fS 是开关频率， ΔI 是电感电流纹波的峰－峰值。通
⋅ fZ1
。
当需要补偿电容 Cc2 时，Cc2 的值由下式确定：
CC2
=
ESR ⋅ CO RC
。
典型应用电路图
杭州士兰微电子股份有限公司 http:
版本号：1.0 2008.09.26 共8页 第7页
封装外形图
SOP-8-225-1.27
SD46520
UNIT: mm
常选择 ΔI 不超过最大输出电流的 30％，以此来确定电感的取值。
同时，还必须满足电感电流的峰值不能超过 2.4A 电流限制值的条件。电感电流的峰值由下式 确定。
ILMAX
= IO
+
1 2
⋅
ΔIL
= IO
+
1 2
⋅
VO ⋅(VI − VO ) VI ⋅ fS ⋅L
。
输入电容选择
降压性DC-DC的输入电流是不连续的，需要在输入端添加输入电容CI保持输入电压的稳定。 输入电容必须是低ESR的电容类型。最好是陶瓷电容，钽电容或低ESR的电解电容也可以。输入 电容值必须大于 10uF。
版本号：1.0 2008.09.26 共8页 第1页
内部框图
SD46520
极限参数
参数 输入电压 开关电压 自举电压 反馈电压 使能端电压 补偿端电压 结温 引脚温度 存储温度
TD1501 3A 150KHZ 45V PWM Buck DC DC 转换器数据表说明书
General DescriptionThe TD1501 is a of easy to use adjustable step-down (buck) switch-mode DC/DC converter. The device is available in an adjustable or fixed output version. It is capable of driving a 3A load with excellent line and load regulation.The output voltage is guaranteed to ±3% tolerance under specified input voltage and output load conditions. The oscillator frequency is guaranteed to ±15%.The PWM control circuit is able to adjust the duty ratio linearly from 0 to 100%. External shutdown is included, featuring typically 80 µA standby current. Self protection features include a two stage frequency reducing current limit for the output switch and an over temperature shutdown for complete protection under fault conditions. Requiring a minimum number of external components, these regulators are simple to use and include internal frequency compensation, and a fixed-frequency oscillator.The TD1501 is available in TO-220B-5L and TO-263-5L packages. Features• Voltage mode non-synchronous PWM control • Built- in switching transistor on chip• Guaranteed 3A output load current• Input voltage range up to 45V• 3,3V,5V and Adjustable output versions• adjustable version output from 1.23V to 42V • Fixed 150KHz frequency internal oscillator• Up to 90% efficiency• ON/OFF shutdown control input• Low power standby mode, I Q typically 80 µA • Thermal shutdown , current limit and short circuit protection• Available in TO-220B and TO-263 packages • RoHS Compliant (100% Green available) • The minimum dropout @ Vout=5V/0.5A up to 0.9 VApplications• Simple High-efficiency step-down regulator• On-card switching regulators• Positive to negative converter• LCD monitor and LCD TV• DVD recorder and PDP TV• Battery charger• Step-down to 1.8/2.5/3.3/5.0 V formicroprocessorsPackage TypesTO220-5LJune, 01, 2013 Rev 2.3 Techcode Semiconductor LimitedPin AssignmentsPin DescriptionsOrdering InformationName DescriptionVin Input supply voltageOutput SwitchingoutputGnd GroundFeedbackOutput voltage feedbackinputON/OFFON/OFF shutdownActive is “Low” or Ground 5 ON/OFF4 Feedback3 Gnd2 Output1 VinGNDTAB ISGNDTO220-5LTO263-5LFunction DescriptionPin Functions+V INThis is the positive input supply for the IC switching regulator. A suitable input bypass capacitor must be present at this pin to minimize voltage transients and to supply the switching currents needed by the regulator.GNDCircuit ground.OutputInternal switch. The voltage at this pin switches between (+V IN – V SAT) and approximately – 0.5V, with a duty cycle of approximately V OUT / V IN. To minimize coupling to sensitive circuitry, the PC board copper area connected to this pin should be kept a minimum.FeedbackSenses the regulated output voltage to complete the feedback loop.ON/OFFAllows the switching regulator circuit to be shutdown using logic level signals thus dropping the total input supply current to approximately 80uA. Pulling this pin below a threshold voltage of approximately 1.3V turns the regulator on, and pulling this pin above 1.3V (up to a maximum of 32V) shuts the regulator down. If this shutdown feature is not needed, the ON /OFF pin can be wired to the ground pin , the regulator will be in the ON condition. The ON /OFF pin should not be left open .Functional Block DiagramFigure 2. Functional Block Diagram of TD1501Typical ApplicationFigure 3. Typical Application of TD1501Absolute Maximum RatingsUnitValueParameter SymbolInput Voltage V IN-0.3 to 45 VFeedback Pin Voltage V FB-0.3 to 40 VEnable Pin Voltage Von-off -0.3 to 40 VOutput Voltage to Ground (Steady State)e V OUT-1 V Power Dissipation P D Internally limited mWOperating Junction Temperature T J150 ºC Storage Temperature T STG-65 to 150 ºCLead Temperature (Soldering, 10 sec) T LEAD260 ºCESD (HBM) V ESD2000 VNote1: Stresses greater than those listed under Maximum Ratings may cause permanent damage tothe device. This is a stress rating only and functional operation of the device at these or any other conditions above those indicated in the operation is not implied. Exposure to absolute maximumrating conditions for extended periods may affect reliability.Recommended Operating ConditionsUnitMax.Parameter SymbolMin.Input Voltage V IN 3.6 45 V Operating Junction Temperature T J -40 125 ºC Operating Ambient Temperature T A -40 85 ºCElectrical Characteristics (All Output Voltage Versions)Unless otherwise specified, VIN = 12V for 3.3V, 5V, adjustable version . I LOAD = 0.5A Ta = 25ºC.Symbol ParameterConditionsMin. Typ. Max. UnitV IN Input voltage 4.5 45 VI Q Quiescent current V FB =12V force driver off34mAOutput=0VNo outside circuitV FB =12V force driver off50 uAI LOutput=-1VOutputleakage currentV IN =40V 2 30 mAI STBYStandby quiescentcurrentON/OFF pin=5V, V IN =32V80 200uAFosc Oscillator Frequency 125 150 170 KHz FSCPOscillator Frequency of Short Circuit ProtectWhen current limit occurred and VFB < 0.5V, Ta = 25℃ 10 30 50 KHz V SAT Saturation voltageI OUT =3ANo outside circuitV FB = 0V force driver on 1.16 1.4 V Max. Duty Cycle (ON)V FB = 0V force driver on 100 DCMin. Duty Cycle (OFF) V FB =12V force driver off% V FBFeedback Voltage V IN = 4.5V to 45 V1.21 1.235 1.26VI FB Feedback bias current V FB =1.3V(Adjustable version only)10 50 nAI CL Current LimitPeak Current (V FB =0V) 3.8 5.5 A V IL Low (Regulator ON) 1.30.6V V IH ON/OFF pin logic inputThreshold voltage High (Regulator OFF)2.01.3VI H ON/OFF pin logic input currentV LOGIC =2.5V(OFF)-0.01 uA I L ON/OFF pin input currentV LOGIC =0.5V(ON) -0.1 uA θJC Thermal ResistanceTO220B-5LTO263-5L Junction toCase2.53.5OC/W θJA Thermal Resistance with a copper area of approximately 3 in 2TO220B-5L TO263-5LJunction to Ambient2823OC/WElectrical Characteristics ( Continued )Specifications with boldface type are for full operationg temperature range, the other type are for T J=25O C.Typical Performance CharacteristicsFigure 4. Efficiency vs. Load (Vin=12V)Figure 5. Output Voltage vs. TemperatureFigure 6. Output Saturation Characteristics Figure 7. Switching Frequency vs. TemperatureFigure 9. ON/OFF Pin Voltage Figure 10. ON/OFF Pin Sink CurrentFigure 8. Quiescent Current vs. TemperatureFigure 11. Output Saturation CharacteristicsTypical Application Circuit (3.3V Fixed Output Voltage Version)Output ComponentInput Voltage Inductor(L1)Through HoleElectrolytic(Cout)Surface MountTantalum(Cout)Schottky Diode(D1)4.5V ~ 18V 47uh 470uf/25V 330uf/6.3V 18V ~ 45V 68uh 560uf/25V 330uf/6.3V ref. Table 5Figure 11. Typical Application of TD1501 For 3.3VTable 1. TD1501 Series Buck Regulator Design Procedure For 3.3VTypical Application Circuit (5V Fixed Output Voltage Version)Output ComponentInput Voltage Inductor(L1)Through HoleElectrolytic(Cout)Surface MountTantalum(Cout)Schottky Diode(D1)7V ~ 18V 33uh 330uf/25V 220uf/10V 18V ~ 45V 47uh 470uf/25V 330uf/10V ref. Table 5Figure 12. Typical Application of TD1501 For 5VTable 2. TD1501 Series Buck Regulator Design Procedure For 5VTypical Application Circuit (Adjustable Output Voltage Version)Vout R1 R2 Cf (Optional)3.3V 1.6K 2.7K33nf 5V 3.6K 11K 10nf 9V 6.8K43K 1.5nf 12V 1.5K 13K1nfOutput ComponentOutputVoltage Input Voltage Inductor (L1)Through Hole Electrolytic (Cout) Schottky Diode( D1 )4.5V ~ 18V 47uh 470uf/25V 3.3V 18V ~45V 68uh 560uf/25V 7V ~ 18V 33uh 330uf/25V 5V 18V ~45V 47uh 470uf/25V 12V ~18V 47uh 330uf/25V 9V 18V ~45V 47uh 470uf/25V 15V ~ 18V 47uh 220uf/25V 12V18V ~45V47uh330uf/25Vref. Table 5Figure 13. Typical Application of TD1501 For ADJ Table 3. Vout VS. R1, R2, Cf Select Table Table 4. Typical Application Buck Regulator Design ProcedureSchottky Rectifier Selection GuideVin2A Load Current 3A Load Current(Max) Part Number Package Vendor Part Number Package Vendor B220/A SMB/SMA 1 B320/B/ASMC/B/A 1 SS22 SMA 2,3 SS32 SMC 2,320 V- - - MBRS320 SMC 4- - - SK32 SMC 6- - - IN5820 D0-201AD 6 B230/A SMB 1 B330/B/ASMC/B/A 1 SS23 SMB 2,3 SS33 SMC 2,330 V20BQ030 SMB 4 MBRS330SMC 4,5 MBRS230 SMB 5 SK33 SMC 3,6SK23 SMB 6 IN5821 D0-201AD 2,6B240/A SMB/SMA 1 B340/B/ASMC/B/A 1 SS24 SMB 2,3,5 SS34 SMC 2,3MBRS240 SMB 5 30BQ040SMC 440 V- - - MBRS340TRSMC 4,5- - - SK34 SMC 6- - - IN5822 DC-201AD 6 B250/A SMB/SMA 1 B350/B/ASMC/B/A 1 SS25 SMB 2,3 SS35 SMC 2,350 VSK23 SMB 6 MBRS330SMC 4,5- - - SK35 SMC 3,64A Load Current 5A Load CurrentVin(Max) Part Number Package Vendor Part Number Package Vendor SL42 SMC 2,3 B520C SMC 1- - - SR502 D0-201AD 120 V- - - SB520 D0-201AD 2- - - IN5823 D0-201AD 6 SL43 SMC 2,3 B530C SMC 1- - - SR503 D0-201AD 130 V- - - SB530 D0-201AD 2,- - - SSC53L SMC 3- - - IN5824 D0-201AD 6 SL44 SMC 2,3,5 B540C SMC 1- - - SR504 D0-201AD 1- - - SB540 DC-201AD 240 V- - - SSC54 SMC 3- - - MBRS540T3 SMC 5- - - IN5825 DC-201AD 6- - - B550C SMC 150 V- - - SB550 DC-201AD 2- - - - - -Table 5 Lists some rectifier manufacturers.No. Vendor WebSiteInc. 1 Diodes,2 FairchildSemiconductor Semiconductor 3 GeneralRectifier 4 International5 OnSemiconductor 6 Pan Jit International Table 6 Schottky Diode manufacturers.Application Hints and Layout GuidelinesHeat Sink / Thermal ConsiderationsThe TD1501 is available in two packages, a 5-pin TO-220B/TO220 and a 5-pin surface mount TO-263. The TO-220B/TO220 package needs a heat sink under most conditions. The size of the heatsink depends on the input voltage, the output voltage, the load current and the ambient temperature. The TD1501 junction temperature rises above ambient temperature for a 3A load and different input and output voltages. The data for these curves was taken with the TD1501 (TO-220B/TO220 package) operating as a buck switching regulator in an ambient temperature of 25o C (still air). These temperature rise numbers are all approximate and there are many factors that can affect these temperatures. Higher ambient temperatures require more heat sinking.The TO-263 surface mount package tab is designed to be soldered to the copper on a printed circuit board. The copper and the board are the heat sink for this package and the other heat producing components, such as the catch diode and inductor. The PC board copper area that the package is soldered to should be at least 0.4 in2, and ideally should have 2 or more square inches of 2 oz. Additional copper area improves the thermal characteristics, but with copper areas greater than approximately 6 in2, only small improvements in heat dissipation are realized. If further thermal improvements are needed, double sided, multilayer PC board with large copper areas and/or airflow are recommended.The TD1501 (TO-263 package) junction temperature rise above ambient temperature with a 3A load for various input and output voltages. This data was taken with the circuit operating as a buck switching regulator with all components mounted on a PC board to simulate the junction temperature under actual operating conditions. This curve can be used for a quick check for the approximate junction temperature for various conditions, but be aware that there are many factors that can affect the junction temperature. When load currents higher than 3A are used, double sided or multilayer PC boards with large copper areas and/or airflow might be needed, especially for high ambient temperatures and high output voltages.For the best thermal performance, wide copper traces and generous amounts of printed circuit board copper should be used in the board layout. (Once exception to this is the output (switch) pin, which should not have large areas of copper.) Large areas of copper provide the best transfer of heat (lower thermal resistance) to the surrounding air, and moving air lowers the thermal resistance even further. Output Voltage Ripple and TransientsThe output voltage of a switching power supply will contain a sawtooth ripple voltage at the switcher frequency, typically about 1% of the output voltage, and may also contain short voltage spikes at the peaks of the sawtooth waveform.The output ripple voltage is due mainly to the inductor sawtooth ripple current multiplied by the ESR of the output capacitor.The voltage spikes are present because of the fast switching action of the output switch, and the parasitic inductance of the output filter capacitor, To minimize these voltage spikes, special low inductance capacitors can be used, and their lead lengths must be kept short. Wiring inductance, stray capacitance, as well as the scope probe used to evaluate these transients, all contribute to the amplitude of these spikes.A large value inductor will also result in lower output ripple voltage , but will have a larger physical size,higher series reistance,and/or lower saturation current. An additional small LC filter can be added to the output (as shown in Figure 14) to further reduce the amount of output ripple and transients.Layout GuidelinesAs in any switching regulator, layout is very important. Rapidly switching currents associated with wiring inductance can generate voltage transients which can cause problems. For minimal inductance and ground loops, the wires indicated by heavy lines should be wide printed circuit traces and should be kept as short as possible. For best results, external components should be located as close to the switcher IC as possible using ground plane construction or single point grounding.If open core inductors are used, special care must be taken as to the location and positioning of this type of inductor. Allowing the inductor flux to intersect sensitive feedback, IC groundpath and C OUT wiring can cause problems.When using the adjustable version, special care must be taken as to the location of the feedback resistors and the associated wiring. Physically locate both resistors near the IC, and route the wiring away form the inductor especially an open core type of inductor.Figure 14, Layout Guidelines and Post Ripple FilterTDxxxxxTDxxxxxPackage Information (TO220B-5L)Dimensions In Millimeters Dimensions In Inches SymbolMin. Max. Min. Max.A 0.44 0.47 0.175 0.185b 0.07 0.09 0.027 0.037D 0.84 0.89 0.330 0.350d1 0.10 0.039d2 0.63 0.248E 9.91 10.41 0.390 0.410e 0.16 0.18 0.062 0.072F 0.12 0.13 0.048 0.052H1 0.64 0.250H2 2.08 2.24 0.820 0.880H3 2.39 2.55 0.942 1.002J1 0.27 0.105J2 0.37 0.53 0.147 0.207J3 0.84 0.331Q 0.25 0.30 0.100 0.120Package Information (TO220-5L)Package Information (TO263-5L)Dimensions In Millimeters Dimensions In Inches SymbolMin. Max. Min. Max.A 4.45 4.7 0.175 0.185B 0.71 0.97 0.028 0.038C 0.38 0.76 0.015 0.030C2 1.22 1.32 0.048 0.052D 8.38 8.89 0.330 0.350E 9.91 10.16 0.390 0.410e 1.57 1.85 0.062 0.070F 6.61 7.11 0.260 0.280L - 14.35 - 0.565L2 - 1.27 - 0.050Packing InformationTO263-5L Carrier Tape Outline DimensionsCarrier Tape, Number of Components Per Reel and Reel SizePackage Carrier Width (W) Pitch (P) Part Per Full Reel Reel Size TO263-5L 24.0 ± 0.1mm 4.0 ± 0.1mm 800 PCS 330 ± 2mm。
315VNSN820M35E中文资料(Nippon Chemi-Con)中文数据手册「EasyDatasheet - 矽搜」
(at 120Hz) The following specifications shall be satisfied when the capacitors are restored to 20C after subjected to DC voltage with the rated ripple current is applied for 3000 hours (2000 hours for F20mm products) at 105C. Capacitance change [P20% of the initial value DF (tanE) [200% of the initial specified value [The initial specified value Leakage current The following specifications shall be satisfied when the capacitors are restored to 20C after exposing them for 1000 hours at 105C without voltage applied. Capacitance change [P15% of the initial value [150% of the initial specified value DF (tanE) Leakage current [The initial specified value
22B25 1.00 22B25 1.20 22B30 1.35 22B35 1.50 22B40 1.67 22B45 1.78 22B50 2.04
30B20 1.15 30B20 1.20 30B25 1.50 30B25 1.67 30B30 1.78 30B30 2.04 30B35 2.30 30B40 2.55 30B45 2.90 30B60 3.49
凌特降压型DC-DC转换器
凌特降压型DC/DC转换器
2006 年8 月15 日－北京－凌特公司（Linear Technology Corporation）推出高效率、2.25MHz、同步降压型稳压器LTC3549，该器件能用低至1.6V 的输入电压提供高达250mA 的连续输出电流。
LTC3549 采用恒定频率和电流模式架构，用 1.6V 至 5.5V 的输入电压工作，非常适用于单节锂离子或两节碱性/镍镉/镍氢电池应用。
该器件可以产生低至0.61V 的输出电压，因此能够为最新一代低压DSP 和微控制器供电。
其2.25MHz 开关频率允许利用高度低于1mm 的纤巧和低成本陶瓷电容器和电感器，因而可为手持式应用组成占板面积非常紧凑的解决方案。
LTC3549 采用RDS(ON) 仅为0.4Ω（N 沟道）和0.56Ω（P 沟道）的内部开关，具有高达93% 的效率。
它还采用低压差100% 占空比工作模式，允许输出电压等于VIN，从而进一步延长了电池工作时间。
LTC3549 利用低纹波突发模式（Burst Mode®）工作，以低于20mVPK-PK 的输出纹波提供仅为50uA 的无负载静态电流。
如果应用是噪声敏感的，那么LTC3549 还可以设置为噪声更低的脉冲跳跃模式，而且仍然提供仅为300uA 的静态电流。
两种器件都保持停机电流低于1uA，从而进一步延长了电池寿命。
LTC3549 用陶瓷电容器可稳定，因而实现了非常低的输出电压纹波。
其它特点包括实现卓越电压和负载瞬态响应的电流模式工作、内部软启动以及过热保护。
MP1584
MP15843A, 1.5MHz, 28V Step-Down ConverterMPS CONFIDENTIAL AND PROPRIETARY INFORMATION – INTERNAL USE ONLYThe Future of Analog IC Technology DESCRIPTIONThe MP1584 is a high frequency step-downFEATURES• Wide 4.5V to 28V Operating Input Range OUTPUT CURRENT (A)ORDERING INFORMATIONPart Number* Package Top Marking Temperature MP1584EN SOIC8E MP1584EN –20°C to +85°CELECTRICAL CHARACTERISTICSV IN = 12V, V EN = 2.5V, V COMP = 1.4V, T A= +25°C, unless otherwise noted.PIN FUNCTIONSTYPICAL PERFORMANCE CHARACTERISTICSV IN = 12V, V OUT=5V, C1 = 10µF, C2 = 22µF, L1= 10µH, T A = +25°C, unless otherwise noted.1v.OUT SW OUT SW2v.2v.Oscillating Frequency vs R freqTYPICAL PERFORMANCE CHARACTERISTICS (continued)V IN = 12V, C1 = 10µF, C2 = 22µF, L1 = 10µH, f SW =500KHz, and T A = +25°C, unless otherwise noted.5ms/div.Startup1ms/div.Shutdown5ms/div.Startup5ms/div.BLOCK DIAGRAMError AmplifierThe error amplifier compares the FB pin voltage with the internal reference (REF) and outputs a current proportional to the difference between the two. This output current is then used to Internal Soft-StartThe soft-start is implemented to prevent the converter output voltage from overshooting during startup. When the chip starts, the internal circuitry generates a soft-start voltageAt higher duty cycle operation condition, the time period available to the bootstrap charging is less so the bootstrap capacitor may not be sufficiently charged.In case the internal circuit does not haveStartup and ShutdownIf both VIN and EN are higher than their appropriate thresholds, the chip starts. The reference block starts first, generating stable reference voltage and currents, and then theAPPLICATION INFORMATIONCOMPONENT SELECTIONSetting the Output VoltageThe output voltage is set using a resistiveA good rule for determining the inductance to use is to allow the peak-to-peak ripple current in the inductor to be approximately 30% of theTable 1—Inductor Selection GuideThe input capacitor (C1) can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor, i.e. 0.1μF, should be placed as close to the IC as possible. When usingMP1584 can be optimized for a wide range of capacitance and ESR values.Compensation ComponentsMP1584 employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the COMP pin. COMP pin isIn this case (as shown in Figure 2), a third pole set by the compensation capacitor (C6) and the compensation resistor (R3) is used to compensate the effect of the ESR zero on the loop gain. This pole is located at:1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine the R3 value by the following equation:OUTC V f 2C 23R ×××π=High Frequency OperationThe switching frequency of MP1584 can be programmed up to 1.5MHz with an external resistor.With higher switching frequencies, the inductiveExternal Bootstrap DiodeIt is recommended that an external bootstrap diode be added when the input voltage is no greater than 5V or the 5V rail is available in the system. This helps improve the efficiency of theTYPICAL APPLICATION CIRCUITSC4NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that thirdparty Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications.PACKAGE INFORMATIONSOIC8E (EXPOSED PAD)5) DRAWING CONFORMS TO JEDEC MS-012, VARIATION BA. 6) DRAWING IS NOT TO SCALE.RECOMMENDED LAND PATTERN。
XL1507 150KHz 40V 3A开关电流降压型DC-DC转换器说明书
150KHz 40V 3A开关电流降压型DC-DC转换器XL1507特点⏹ 4.5V到40V宽输入电压范围⏹输出版本固定5V和ADJ可调⏹输出电压1.23V到37V可调⏹最大占空比100%⏹最小压差1.5V⏹固定150KHz开关频率⏹最大3A开关电流⏹内置功率三极管⏹高效率⏹出色的线性与负载调整率⏹EN脚TTL关机功能⏹EN脚迟滞功能⏹内置热关断功能⏹内置限流功能⏹内置二次限流功能⏹TO252-5L封装应用⏹LCD电视与显示屏⏹数码相框⏹机顶盒⏹路由器⏹通讯设备供电描述XL1507是一款高效降压型DC-DC转换器，固定150KHz开关频率，可以提供最高3A输出电流能力，具有低纹波，出色的线性调整率与负载调整率特点。
XL1507内置固定频率振荡器与频率补偿电路，简化了电路设计。
PWM控制环路可以调节占空比从0~100%之间线性变化。
内置使能功能、输出过电流保护功能。
当二次限流功能启用时，开关频率从150KHz降至50KHz。
内部补偿模块可以减少外围元器件数量。
图1.XL1507封装150KHz 40V 3A 开关电流降压型DC-DC 转换器 XL1507引脚配置EN GND SW VINFB 12345TO252-5LMetal Tab GND图2. XL1507引脚配置表1.引脚说明引脚号 引脚名称 描述1 VIN 电源输入引脚，支持DC4.5V~40V 宽范围电压操作，需要在VIN 与GND 之间并联电解电容以消除噪声。
2 SW 功率开关输出引脚，SW 是输出功率的开关节点。
3 GND 接地引脚。
4 FB 反馈引脚，通过外部电阻分压网络，检测输出电压进行调整，参考电压为1.23V 。
5 EN使能引脚，低电平工作，高电平关机，悬空时为低电平。
150KHz 40V 3A 开关电流降压型DC-DC 转换器 XL1507方框图EA1.23V ReferenceGNDFB3.3V 1.23VEA COMPOscillator 150KHz3.3V Regulator Start UpLatchCOMP2COMP1DriverThermal ShutdowninENSW220mV 200mV44m ΩCurrent LimitR2R1=2.5K5V R2=7.6KADJ R2=0 R1=OPENSwitch图3. XL1507方框图典型应用XL1507-5.0CIN 470uf 35VC1 105330uf 35VD1 L1 33uh/3A+12VLOAD13524GNDVINFBSWEN ON OFF 5V/3ACOUT 1N5820图4. XL1507系统参数测量电路（12V-5V/3A ）150KHz 40V 3A 开关电流降压型DC-DC 转换器 XL1507订购信息产品型号 打印名称封装方式包装类型 XL1507-ADJE1 XL1507-ADJE1 TO252-5L 2500只每卷 XL1507-5.0E1 XL1507-5.0E1TO252-5L2500只每卷XLSEMI 无铅产品，产品型号带有“E1”后缀的符合RoHS 标准。
LN2952A V2.6中文 -SNY
L N 2952A2A, 18V 同步整流降压转换器概述LN2952A是一款单片同步整流降压稳压器，它集成了导通阻抗130mΩ的MOSFET，可以在很宽的输入电压范围（4.75V-18V）内提供2A的负载能力。
电流模式控制使其具有很好的瞬态响应和单周期内的限流功能。
可调的软启动时间能避免开启瞬间的冲击电流，在停机模式下，输入电流小于1uA。
LN2952A封装为SOP8-PP, 同时提供了紧凑的系统方案，可以最大限度的减少外围元件。
应用z分立式电源系统z网络系统z FPGA, DSP, ASIC电源z绿色电子产品z笔记本电脑特性z2A输出电流z输入电压范围4.75V到18Vz内部集成130mΩ的功率MOSFETz输出可调范围为0.925V到15Vz效率可达95%z可调软启动时间z外围使用低ESR瓷片电容可保证其稳定工作z固定的450kHz工作频率z每个周期内都有限流功能z具有欠压保护功能z散热能力较强的SOP8-PP封装封装SOP8-PP典型应用电路图图1 典型应用电路图典型效率曲线η vs Io(Vo=5V)图2 典型效率曲线引脚说明引脚序号引脚名称引脚描述1 BS 上管栅极驱动升压输入。
BS为上管N沟道MOSFET开关提供驱动。
从SW到BS 端连接一个0.01uF或更大的电容。
2 IN 电源输入。
为IC以及降压转换器开关提供输入电源。
在4.75V至18V的电压范围驱动IN。
通过一个适当的大电容旁路IN到地，以消除输入IC的噪声。
3 SW 功率开关输出。
SW为开关节点提供电源输出。
从SW端到输出负载连接输出LC 滤波器。
请注意，从SW到BS需要接一个电容。
4 GND电源地(连接裸露焊盘到4引脚)。
5 FB 反馈输入端。
FB感应输出电压来调节这个电压。
通过来自输出电压的一个电阻分压器驱动FB。
反馈阈值电压是0.925V。
6 COMP 补偿节点。
COMP用来补偿调节控制回路。
从COMP脚到GND连接一个RC网络来补偿调节控制回路。
24V转5V降压芯片,24V转3.3V的稳压芯片,中文规格书
过电流保护和短路 当电感器电流峰值超过设置电流限制阈值。同时，输出电压开始下降，直到 FB 低于欠电压 （UV）阈值，通常低于参考值 25%。一旦一个紫外线被触发，就会进入打嗝模式以定期重 新启动部件。当输出为对地完全短路。平均短路电流大大降低，以减轻热并保护监管者。一 旦过电流情况出现，则退出 hiccup 模式远离的。
特征
⚫ 宽 4V 至 30V 工作输入范围 ⚫ 1.2A 连续输出电流 ⚫ 1.4MHz 开关频率 ⚫ 短路保护模式 ⚫ 内置过流限制 ⚫ 内置过电压保护 ⚫ 力模式 PWM ⚫ 内部软启动 ⚫ 200mΩ/150mΩ低 RDS（ON）内部功率金氧半电晶体 ⚫ 0.8V 输出可调 ⚫ 不需要肖特基二极管 ⚫ 综合内部补偿 ⚫ 热关机 ⚫ 提供 SOT23-6 套装 ⚫ -40°C 至+85°C 温度范围
绝对最大额定值（注 1/2）
VIN，EN，电压
-0.3Vto36V
VFB 电压
工作温度范围 铅温度（焊接，10s） ESD（人体制造）HMB VSW 电压 VBS 电压 储存温度范围 结温 ESD（机械制造）MM RθJA RθJC 注： （1） 超过这些额定值可能会损坏设备。 （2） 不能保证设备在其工作条件外正常工作。
误差放大器 误差放大器将 FB 引脚电压与内部 FB 基准（VFB）进行比较，并输出 a 电流与两者之差成正 比。该输出电流随后用于充电或放电内部补偿网络，这是用来控制功率 MOSFET 电流。优化 后的内部补偿网络使外部元件的数量和简化了控制回路设计。
内部软启动 软启动是为了防止变频器输出电压在启动。当芯片启动时，内部电路产生一个软启动电压 （SS）上升从 0V 到 0.807V。当低于内部参考（REF）时，SS 覆盖 REF，因此错误发生放大器 以 SS 为基准。当 SS 高于 REF 时，REF 恢复控制。时间就是时间内部最大为 1.2ms。
MP2303A中文翻译
MPS模拟IC科技的未来3A,28V,360KHZ同步整流降压调节器描述MP2303A是一个单片的同步整流调节器，器件通过集成了一个150MΩ的上臂MOSFET和一个80M Ω的下臂MOSFET使其能够在4.7V到28V的宽输入电压中提供3A的连续负载电流。
电流模式控制提供快速瞬态响应和周期的电流限制。
一个可调的软启动可预防启动时的电流浪涌。
在关机模式，其提供电流低于1UA.该器件提供8脚SOIC和PDIP-8两种封装，依赖非常少的外部器件以提供紧凑的系统解决方案特性*3A输出电流* 4.7V-28V宽输入工作电压*集成MOSFET开关器件*输出从0.8V-25V可调*转换效率可达95%*可编程软起动*稳定的低ESR陶瓷输出电容*固定360KHZ频率*周期电流过载保护*增强散热的8PIN SOIC和PDIP-8封装应用*分布式电源系统*预调节的线性调节器（PRE-REGULATOR FOR LINEAR REGULATORS)*笔记本电脑典型应用效率和输出电流典型应用效率和输出电流订货信息型号封装顶部标示储存温度*后缀-Z 的是胶带和卷轴（例如MP2303ADN-Z)后缀-LF 的是遵守ROHS 的封装（例如MP2303ADN-LF-Z)**后缀-Z 的是胶带和卷轴（例如MP2303ADN-Z)后缀-LF 的是遵守ROHS 的封装（例如MP2303ADN-LF-Z)封装参考极限参数供电电压………………V IN -0.3V 到+30V开关电压………………V SW -1V 到VIN+0.3VBOOST 电压…………V BS V SW -0.3V 到V SW +6V其他所有引脚………………-0.3V 到+6V结温…………………………150℃连续耗散功率SOIC8E …………………………2.5WPDIP8…………………………1.2W引脚温度……………………260℃储存温度………………-65℃到+150℃推荐工作条件输入电压V IN …………4.7V 到28V输出电压V OUT …………0.8V 到25V最大结温………………+125℃热电阻ΘJ A ΘJ C SOIC8E ……………50……10℃/W PDIP8………………105……45℃/W 1）超出这些参数可能损坏器件2）最大允许耗散功率是最大结温T J （MAX ）、环境结温热电阻、环境温度的函数。
NB680 28V、低Iq、高电流、固定3.3V-8A同步降压转换器说明书
NB68028V, Low Iq, High Current, Fixed 3.3V-8ASynchronous Buck ConverterDESCRIPTIONThe NB680 is a fully integrated, high-frequency, synchronous, rectified, step-down, switch-mode converter with a fixed 3.3 V Vout. It offers a very compact solution to achieve an 8 A continuous output current and a 10 A peak output current over a wide input supply range with excellent load and line regulation.The NB680 operates at high efficiency over a wide output current load range based on MPS proprietary switching loss reduction technology and internal low Ron power MOSFETs. Adaptive constant-on-time (COT) control mode provides fast transient response and eases loop stabilization. The DC auto-tune loop provides good load and line regulation.NB680 provides a fixed 3.3 V LDO, which can power the external peripheries, such as the keyboard controller in the laptop.Also, a 250 kHz CLK is available; its output can drive an external charge pump, generating gate drive voltage for the load switches without reducing the main converter’s eff iciency.Full protection features include OC limit, OVP,UVP, and thermal shutdown.NB680 requires a minimum number of externalcomponents and is available in a QFN2mm x 3mm package.FEATURES∙ Wide 4.8 V to 28 V Operating Input Range ∙ Fixed 3.3 V Vout∙ Ultrasonic Mode with Fs over 25 kHz ∙ 100 μA Low Quiescent Current ∙ 8 A Continous Output Current ∙ 10 A Peak Output Current∙ Adaptive COT for Fast Transient ∙ DC Auto-Tune Loop∙ Stable with POSCAP and Ceramic Output Capacitors∙ 250 kHz CLK for External Charge Pump ∙ Built-In 3.3 V, 100 mA LDO with Switch Over∙ 1% Reference Voltage ∙ Internal Soft Start ∙ Output Discharge∙ 700 kHZ Switching Frequency∙ OCL, OVP, UVP, and Thermal Shutdown. ∙ Latch-Off Reset via EN or Power Cycle. ∙QFN 2mm x 3mm Package APPLICATIONS∙ Laptop Computers ∙ Tablet PCs∙ Networking Systems ∙Servers∙Personal Video Recorders∙Flat Panel Television and Monitors ∙Distributed Power SystemsAll MPS parts are lead-free, halogen-free, and adhere to the RoHS directive. For MPS green status, please visit the MPS website under Quality Assurance. “MPS” and “The Future of Analog IC Technology” are registered trademarks of Monolithic Power Systems, Inc.TYPICAL APPLICATIONORDERING INFORMATION* For Tape & Reel, add suffix –Z (e.g. NB680GD –Z)TOP MARKINGALV: Product code of NB680GD Y: Year code LLL: Lot numberPACKAGE REFERENCEABSOLUTE MAXIMUM RATINGS (1) Supply voltage (V IN) .................................... 28 V V SW (DC) ......................................... -1 V to 26 V V SW (25 ns) .................................. -3.6 V to 28 V V BST ................................................. V SW + 4.5 V All other pins ............................. -0.3 V to +4.5 V Continuous power dissipation (T A=+25°C) (2) QFN-12 (2mm x 3mm) .............................. 1.8 W Junction temperature ............................... 150︒C Lead temperature .................................... 260︒C Storage temperature ................ -65︒C to +150︒C Recommended Operating Conditions (3) Supply voltage .............................. 4.8 V to 24 V Operating junction temp. (T J). .. -40°C to +125°C Thermal Resistance (4)θJA θJCQFN-12 (2mm x 3mm) ........... 70 ...... 15 ... ︒C/W NOTES:1) Exceeding these ratings may damage the device.2) The maximum allowable power dissipation is a function of themaximum junction temperature T J(MAX), the junction-to-ambient thermal resistance θJA, and the ambient temperature T A. The maximum allowable continuous power dissipation at any ambient temperature is calculated by P D(MAX)=(T J(MAX)-T A)/θJA. Exceeding the maximum allowable power dissipation produces an excessive die temperature, causing the regulator to go into thermal shutdown. Internal thermal shutdown circuitry protects the device from permanent damage.3) The device is not guaranteed to function outside of itsoperating conditions.4) Measured on JESD51-7, 4-layer PCB.ELECTRICAL CHARACTERISTICS V = 12 V, T = 25 C, unless otherwise noted.ELECTRICAL CHARACTERISTICS (continued) V = 12 V, T = 25︒C, unless otherwise noted.NOTE:5) Guaranteed by design.PIN FUNCTIONS NB680V IN = 12 V, V OUT = 3.3 V, L = 1.5 µH/10 mΩ, F S = 700 kHz, T J=+25°C, unless otherwise noted.V IN = 12 V, V OUT = 3.3 V, L = 1.5 µH/10 mΩ, F S = 700 kHz, T J=+25°C, unless otherwise noted.V IN=12 V, V OUT =3.3 V, L=1.5 µH/10 mΩ, F S=700 kHz, T J=+25°C, unless otherwise noted.FUNCTIONAL BLOCK DIAGRAMNB680Figure 1—Functional block diagramOPERATIONPWM OperationThe NB680 is a fully integrated, synchronous, rectified, step-down, switch-mode converter with a fixed 3.3 V output. Constant-on-time (COT) control provides fast transient response and eases loop stabilization. At the beginning of each cycle, the high-side MOSFET (HS-FET) is turned on when the feedback voltage (V FB) is below the reference voltage (V REF), which indicates insufficient output voltage. The on period is determined by the output voltage and the input voltage to make the switching frequency fairly constant over the input voltage range.After the on period elapses, the HS-FET is turned off or enters an off state. It is turned on again when V FB drops below V REF. By repeating operation this way, the converter regulates the output voltage. The integrated low-side MOSFET (LS-FET) is turned on when the HS-FET is in its off state to minimize the conduction loss. There is a dead short between the input and GND if both the HS-FET and the LS-FET are turned on at the same time (shoot-through). In order to avoid shoot-through, a dead time (DT) is generated internally between the HS-FET off and the LS-FET on period or the LS-FET off and the HS-FET on period.Internal compensation is applied for COT control for stable operation even when ceramic capacitors are used as output capacitors. This internal compensation improves the jitter performance without affecting the line or load regulation.CCM OperationFigure 2—CCM operationContinuous conduction mode (CCM) occurswhen the output current is high, and the inductorcurrent is always above zero amps (see Figure 2).When V FB is below V REF, the HS-FET is turned onfor a fixed interval. When the HS-FET is turnedoff, the LS-FET is turned on until the next period.In CCM operation, the switching frequency isfairly constant (PWM mode).DCM OperationWith the load decreases, the inductor current willdecrease as well. Once the inductor currentreaches zero, the device transitions from CCM todiscontinuous conduction mode (DCM).DCM operation is shown in Figure 3. When V FB isbelow V REF, the HS-FET is turned on for a fixedinterval, which is determined by the one-shot ontimer. See Equation (1). When the HS-FET isturned off, the LS-FET is turned on until theinductor current reaches zero. In DCM operation,the V FB does not reach V REF when the inductorcurrent is approaching zero. The LS-FET driverturns into tri-state (high Z) whenever the inductorcurrent reaches zero. A current modulator takesover the control of the LS-FET and limits theinductor current to less than -1 mA. Hence, theoutput capacitors discharge slowly to GNDthrough the LS-FET. As a result, the efficiencyduring a light-load condition is improved greatly.The HS-FET is not turned on as frequently duringa light-load condition as it is during a heavy-loadcondition (skip mode).At a light-load or no-load condition, the outputdrops very slowly, and the NB680 reduces theswitching frequency naturally, achieving highefficiency at light load.Figure 3—DCM OperationAs the output current increases from the light- load condition, the time period within which the current modulator regulates becomes shorter. The HS-FET is turned on more frequently. Hence, the switching frequency increases accordingly. The output current reaches the critical level when the current modulator time is zero. The critical level of the output current is determined with Equation (1):IN OUT OUTOUTSW IN(V V )V I 2L F V -⨯=⨯⨯⨯ (1) The part enters PWM mode once the output current exceeds the critical level. After that, the switching frequency stays fairly constant over the output current range. DC Auto-Tune LoopThe NB680 applies a DC auto-tune loop to balance the DC error between V FB and V REF by adjusting the comparator input REF to make V FB always follow V REF . This loop is quite slow, so it improves the load and line regulation without affecting the transient performance. The relationship between V FB , V REF , and REF is shown in Figure 4.Figure 4—DC auto-tune loop operation Ultrasonic Mode (USM)Ultrasonic mode (USM) keeps the switching frequency above an audible frequency area during light-load or no-load conditions. Once the part detects that both the HS-FET and the LS-FET are off (for about 32 µs), it shrinks the Ton to keep Vout under regulation with optimal efficiency. If the load continues to decrease, the part discharges Vout to make sure FB is less than 102 percent of the internal reference. The HS-FET turns on again once the internal FB reaches VREF and then stops switching.USM is selected by the EN voltage level. When EN is in the range of 1.38 V to 1.8 V, it enters USM. If EN is in the range of 2.6 V to 3.6 V, it enters normal mode.Configuring the EN ControlThe NB680 has two enable pins to control the on/off of the internal regulators and CLK. For NB680, the 3V3 LDO is always on when Vin passes UVLO. EN controls both the buck and the CLK. Once EN is on, the ENCLK is able to control the CLK on/off. See Table1 for the NB680 EN logic control.Table 1—ENCLK/EN controlFor automatic start-up, EN can be pulled up to the input voltage through a resistive voltage divider. Refer to the “UVLO Protection ” section for more details. Soft Start (SS)The NB680 employs a soft-start (SS) mechanism to ensure smooth output during power-up. When EN goes high, the internal reference voltage ramps up gradually; hence, the output voltage ramps up smoothly as well. Once the reference voltage reaches the target value, the soft start finishes, and the part enters steady-state operation.If the output is pre-biased to a certain voltage during start-up, the IC disables the switching of both the high-side and the low-side switches until the voltage on the internal reference exceeds the sensed output voltage at the internal FB node. 3.3 V Linear RegulatorThere is a built-in 100 mA standby linear regulator with a fixed output at 3.3 V, controlled by VIN UVLO. Once Vin passes its UVLO, it is on. The 3.3 V LDO is not controlled by EN or ENCLK. This LDO is intended mainly for an auxiliary 3.3 V supply for the notebook system in standby mode. Add a ceramic capacitor with a value between 4.7 μF and 22 uF placed close to the LDO pins to stabilize the LDOs.LDO Switch OverWhen the output voltage becomes higher than 3.15 V and the power good (PG) is ok, the internal LDO regulator is shut off, and the LDO output is connected to VOUT by the internal switch-over MOSFET, reducing power loss from the LDO.CLK for Charge PumpThe 250 kHz CLK signal drives an external charge pump circuitto generate approximately 10 V-12 V DC voltage. The CLK voltage becomes available once Vin is higher than the UVLO threshold, and ENCLK is pulled high (see Figure 5).Figure 5—Charge pump circuitPower Good (PG)The NB680 has power-good (PG) output used to indicate whether the output voltage of the buck regulator is ready. PG is the open drain of a MOSFET. It should be connected to V CC or another voltage source through a resistor (e.g. 100k). After the input voltage is applied, the MOSFET is turned on so that PG is pulled to GND before SS is ready. Once FB voltage rises to 95 percent of the REF voltage, PG is pulled high after 750 µs.When the FB voltage drops to 85 percent of the REF voltage, PG is pulled low.Over-Current Protection (OCP)NB680 has cycle-by-cycle over-current limiting control. The current-limit circuit employs a "valley" current-sensing algorithm. The part uses the Rds(on) of the LS-FET as a current-sensing element. If the magnitude of the current-sense signal is above the current-limit threshold, the PWM is not allowed to initiate a new cycle. The trip level is fixed internally. The inductor current is monitored by the voltage between GND and SW. GND is used as the positive currentsensing node, so GND should be connected to the source terminal of the bottom MOSFET. Since the comparison is done during the HS-FET off state and the LS-FET on state, the OC trip level sets the valley level of the inductor current. Thus, the load current at the over-current threshold (I OC ) is calculated with Equation (2):∆=+inductorOC I I I_limit 2(2) In an over-current condition, the current to the load exceeds the current to the output capacitor; thus, the output voltage tends to fall off. Eventually, it ends up crossing the under-voltage protection threshold and shuts down. Fault latching can be reset by EN going low or the power cycling of VIN.Over/Under-Voltage Protection (OVP/UVP) NB680 monitors the output voltage to detect over and under voltage. Once the feedback voltage becomes higher than 122 percent of the target voltage, the OVP comparator output goes high, and the circuit latches as the HS-FET driver turns off, and the LS-FET driver turns on, acting as an -1.8 A current source.To protect the part from damage, there is an absolute OVP on VOUT (usually set at 6.2 V). Once Vout > 6.2 V, the controller turns off both the HS-FET and the LS-FET. This protection is not latched off and will keep switching once the Vout returns to its normal value.When the feedback voltage drops below 75 percent of the Vref but remains higher than 50 percent of the Vref, the UVP-1 comparator output goes high, and the part latches if the FB voltage remains in this range for about 32 µs (latching the HS-FET off and the LS-FET on). The LS-FET remains on until the inductor current hits zero. During this period, the valley current limit helps control the inductor current.When the feedback voltage drops below 50 percent of the Vref, the UVP-2 comparator output goes high, and the part latches off directly after the comparator and logic delay (latching the HS-FET off and the LS-FET on). The LS-FET remains on until the inductor current hits zero. Fault latching can be re-set by EN going low or the power cycling of VIN.UVLO ProtectionThe part starts up only when the Vin voltage is higher than the UVLO rising threshold voltage. The part shuts down when the VIN is lower than the Vin falling threshold. The UVLO protection is non-latch off. Fault latching can be re-set by EN going low or the power cycling of VIN.If an application requires a higher under-voltage lockout (UVLO), use EN to adjust the input voltage UVLO by using two external resistors (see Figure 6).Figure 6—Adjustable UVLOTo avoid too much sink current on EN, the EN resistor (Rup) is usually in the range of 1 M-2 MΩ.A typical pull-up resistor is 2 MΩ.Thermal ShutdownThermal shutdown is employed in the NB680. The junction temperature of the IC is monitored internally. If the junction temperature exceeds the threshold value (140ºC, typically), the converter shuts off. This is a non-latch protection. There is about 25ºC hysteresis. Once the junction temperature drops to about 115ºC, it initiates a SS.Output DischargeNB680 discharges the output when EN is low, or the controller is turned off by the protection functions UVP, OCP, OCP, OVP, UVLO, and thermal shutdown. The part discharges outputs using an internal MOSFET.APPLICATION INFORMATIONInput CapacitorThe input current to the step-down converter is discontinuous, and therefore requires a capacitor to supply the AC current to the step-down converter while maintaining the DC input voltage. Ceramic capacitors are recommended for best performance and should be placed as close to the V IN pin as possible. Capacitors with X5R and X7R ceramic dielectrics are recommended because they are fairly stable with temperature fluctuations.The capacitors must have a ripple-current rating greater than the maximum input ripple current of the converter. The input ripple current can be estimated with Equation (3) and Equation (4):CIN OUT I I =The worst-case condition occurs at V IN = 2V OUT , where:OUTCIN I I 2=(4) For simplification, choose an input capacitor with an RMS current rating greater than half of the maximum load current.The input capacitance value determines the input voltage ripple of the converter. If there is an input voltage ripple requirement in the system, choose an input capacitor that meets the specification. The input voltage ripple can be estimated with Equation (5) and Equation (6):OUT OUT OUT IN SW IN IN INI V VV (1)F C V V ∆=⨯⨯-⨯ (5)The worst-case condition occurs at V IN = 2V OUT,where:OUT IN SW INI 1V 4F C ∆=⨯⨯ (6)Output CapacitorThe output capacitor is required to maintain the DC output voltage. Ceramic or POSCAP capacitors are recommended. The output voltage ripple can be estimated with Equation (7):OUT OUT OUT ESR SW INSW OUTV V 1V (1)(R )F LV 8F C ∆=⨯-⨯+⨯⨯⨯ (7)When using ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance. The output voltage ripple is caused mainly by the capacitance. For simplification, the output voltage ripple can be estimated using Equation (8):OUT OUT OUT 2SW OUT INV VV (1)8F L C V ∆=⨯-⨯⨯⨯ (8) When using POSCAP capacitors, the ESRdominates the impedance at the switching frequency. The output ripple can be approximated using Equation (9):OUT OUT OUTESRSW INV V V (1)R F L V ∆=⨯-⨯⨯ (9)The maximum output capacitor limitation should be considered in design application. For a small soft-start time period (if the output capacitor value is too high), the output voltage cannot reach the design value during the soft-start time, causing it to fail to regulate. The maximum output capacitor value (C o_max ) can be limited approximately with Equation (10):O _MAX LIM_AVG OUT ss OUT C (I I )T /V =-⨯ (10)Where I LIM_AVG is the average start-up currentduring the soft-start period, and T ss is the soft-start time. InductorThe inductor is necessary to supply constant current to the output load while being driven by the switched input voltage. A larger value inductor results in less ripple current, resulting in a lower output ripple voltage. However, a larger value inductor has a larger physical footprint, a higher series resistance, and/or a lower saturation current. A good rule for determining the inductance value is to design the peak-to-peak ripple current in the inductor to be in the range of 30 percent to 50 percent of the maximum output current, with the peak inductor current below the maximum switch current limit. The inductance value can be calculated with Equation (11): OUT OUT SW L INV VL (1)F I V =⨯-⨯∆ (11)Where ΔI L is the peak-to-peak inductor ripple current.The inductor should not saturate under the maximum inductor peak current (including short current), so it is suggested to choose Isat > 10 A. PCB Layout GuidelinesEfficient PCB layout is critical for optimum IC performance. For best results, refer to Figure 7 and follow the guidelines below:1. Place the high-current paths (GND, IN, andSW) very close to the device with short, direct, and wide traces. The PGND trace should be as wide as possible (This should be the number one priority).2. Place the input capacitors as close to IN andGND as possible on the same layer as the IC. 3. Place the decoupling capacitor as close toVCC and GND as possible. Keep the switching node (SW) short and away from the feedback network.4. Keep the BST voltage path as short aspossible with a >50 mil trace.5. Keep the IN and GND pads connected with alarge copper plane to achieve better thermal performance. Add several vias with 8 mil drill/16 mil copper width close to the IN and GND pads to help thermal dissipation.6. A 4-layer layout is strongly recommended toachieve better thermal performance.Figure 7— Recommend PBC layoutTYPICAL APPLICATIONNOTE: If the charge pump function is not used, leave CLK open.Figure 8—Typical application schematic with ceramic output capacitorsNOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications.PACKAGE INFORMATIONQFN-12 (2mm x 3mm)SIDE VIEWBOTTOM VIEWNOTE:1) ALL DIMENSIONS ARE IN MILLIMETERS.2) EXPOSED PADDLE SIZE DOES NOT INCLUDE MOLD FLASH.3) LEAD COPLANARITY SHALL BE 0.10 MILLIMETERS MAX.4) JEDEC REFERENCE IS MO-220.5) DRAWING IS NOT TO SCALE.TOP VIEW PIN 1 IDINDEX AREARECOMMENDED LAND PATTERN。
电源转换器产品说明说明书
TABILITY50 dB-50 dB0 dB 180°-180°0°100HZ1KhZ10KH 100KHZFREQUENCYPhase GainAll specifications are typical @+25°C with nominal input voltage under full output load conditions, unless otherwise noted. Specifications subject to change without notice./powerconversionIndustrial & military grade high density DC to DC converters4-40 UNC-2B THRU 4 PLACES-C Option-B Option-A Option.040 DIA ± .005.50 / 12.7 MIN..30 / 7.6.38 / 9.7marking surfacebase plate.50 / 12.7MIN..15 / 3.81234+ V IN IN RTN TRIM TTL PAR POWER GOOD+ S 056SYNC7891011+ OUT - OUT - STolerances:inches -x.xx x.xxx= ±0.03= ±0.015mm -x.xx.xx = ±0.8= ±0.401111 Knox Street TorranceCA 90502USATel: +1 310 202 8820*********************All specifications are typical @+25°C with nominal input voltage under full output load conditions, unless otherwise noted. Specifications subject to change without notice./powerconversionPerformance characteristics50 dB-50 dB0 dB How to Order:50 T M / 5 / 15 - A Phase GainNB50TT RIPLEOUTPUT3/powerconversionIndustrial & military grade high density DC to DC converters.125 / 32.875 / 1.275 / 32.391.450 / 36.831.100 / 27.94.925 / 23.504-40 UNC-2B THRU 4 PLACES1.875 / 47.632.00 / 50.8.975 / 24.77 -C Option-B Option-A Option-A Option.040 DIA ± .005.50 / 12.7 MIN..30 / 7.6.38 / 9.7marking surfacebase plate.50 / 12.7MIN..15 / 3.81234+ V IN IN RTN TRIM TTL Inches / MillimetersPOWER GOOD+ S.825 / 20.96.675 / 17.15.375 / 9.53.750 / 19.051.125 / 28.586SYNC7891011+ MAIN OUT MAIN RTN- S.125 / 3.181.625 / 41.28.125 / 3.183.00 / 7121314+ AUX OUT AUX COM - AUX OUT .575 / 14.61.400 / 10.161.875 / 47.63Tolerances:inches -x.xx x.xxx= ±0.03= ±0.015mm -x.xx.xx = ±0.8= ±0.40DCTODC C ONVERTERSAll specifications are typical @+25°C with nominal input voltage under full output load conditions, unless otherwise noted. Specifications subject to change without notice./powerconversionPerformance characteristics50S NB100NB150Performance CharacteristicsIX. TTL Turn OnIII. Efficiency vs. Input VoltageII. Efficiency vs. Output PowerVI. Input Transient ResponseV. Load Transient ResponseIV. Output Voltage RippleVII. Input Inrush CurrentVIII. Input Current RippleX. TTL Turn-offXI. Turn-onXII. Turn-off / Hold-up TimeInput Voltage E f f i c i e n c y100%80%60%40%20%0%90%85%80%75%70%65%60%20% 40% 60% 80% 100%90%85%80%75%70%65%60%14 18 22 26 30 34 38Output Load Input Voltage20 m V /d i vTime: 2 μS/div Time: 0.5 mS/divTime: 0.2 mS/div20 V /d i v 0.2 V /d i vTime: 50 μS/div Time: 2 μS/div Time: 0.5 mS/div20 A /d i v 20 V /d i v0.2 A /d i v5 V /d i v 2 V /d i v10 V /d i v 5 V /d i vTime: 100 μS/divTime: 0.5 mS/divTime: 100 μS/div 5 V /d i v 2 V /d i v5 V /d i v 20 V /d i vV = 28 Vdc, V = 15 Vdc, I = 3.3 AV = 28 Vdc, V = 15 Vdc50 - 100% Step LoadOutput CurrentOutput VoltageOutput VoltageInput VoltageV = 15 Vdc, I = 3.3 A14 - 40V TransientV = 28 Vdc, V = 15Vdc, I = 3.3 AInput VoltageInput CurrentV = 28 Vdc, V = 15 Vdc, I = 3.3 AV = 28 Vdc, V = 15 Vdc, I = 3.3 ATTL SignalOutput VoltageV = 28 Vdc, V = 5 Vdc, I = 3.3 AOutput VoltageInput Voltage V = 28 Vdc, V = 15 Vdc, I = 3.3 AInput VoltageOutput VoltageV = 28 Vdc, V = 15 Vdc, I = 3.3 AOutput VoltageTTL Signal 3.3V5V12V24V15V28V 24V 15V 12V 5V 3.3V2V15V 12V10 11 12 13 4028V2V5/powerconversionNBF50 EMI filtersHow to Order:Inches / Millimeters .125 / 3.181.625 / 41.281.375 / 34.93.625 / 15.88.875 / 22.23.125 / 3.184-40 UNC-2B THRU 4 PLACES 1.50 / 38.11.050 / 26.671.375 / 34.93.450 / 11.43.125 / 3.18-C Option-B Option-A Option-A Option.040 DIA ± .005.50 / 12.7 MIN..30 / 7.6.38 / 9.7marking surfacebase plate.50 / 12.7MIN..15 / 3.81234+ IN- IN+ OUT - OUT1.75 / 44.528V in - 50 wattsMIL-STD-461D, CE102With NBF50Without NBF50CASE DRA WING0.01 0.02 0.04 0.06 0.8 0.1 0.2 0.4 0.6 0.8 1 2 4 6 8 10120100806040200-201201008060402000.03 0.04 0.06 0.08 0.1 0.2 0.4 0.6 0.8 1 2 4 6 8 10dBuA dBuV kHzMHzTolerances:inches -mm-x.xx x.xxx x.x x.xx= ±0.03= ±0.015= ±0.8= ±0.40NBF50>> 181111 Knox Street TorranceCA 90502USATel: +1 310 202 8820*********************All specifications are typical @+25°C with nominal input voltage under full output load conditions, unless otherwise noted. Specifications subject to change without notice.6/powerconversionEaton is a registered trademark. All other trademarks are property of their respective owners.Eaton1000 Eaton Boulevard Cleveland, OH 44122 United States © 2017 EatonAll Rights Reserved March, 2017ore-mail:*******************。
UC1584资料
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20V VFLT Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . 50V, 30V at 2A Supply Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 50mA Analog Inputs. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 to 20V SYNC Maximum Sink Current . . . . . . . . . . . . . . . . . . . . . 600µA PWM Driver, IOUT . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± 300mA PWM Driver, IOUT (Peak) . . . . . . . . . . . . . . . . . . . . . . . . . ± 1.5A Maximum Operating Frequency . . . . . . . . . . . . . . . . . . . . 1MHz Power Dissipation at TA = 60°C . . . . . . . . . . . . . . . . . . . . . . 1W Storage Temperature . . . . . . . . . . . . . . . . . . . . –65°C to 150°C Junction Temperature . . . . . . . . . . . . . . . . . . . . –55°C to 150°C Lead Temperature (Soldering, 10 sec.) . . . . . . . . . . . . . . 300°C Currents are positive into, negative out of specified terminal. Consult Packaging Section of Databook for thermal limitations and considerations of packages.
MP1484 3A、18V、340KHz同步rectified步态降压转换器说明书
3A, 18V, 340KHz Synchronous Rectified Step-Down ConverterDESCRIPTIONThe MP1484 is a monolithic synchronous buck regulator. The device integrates top and bottom 85m Ω MOSFETS that provide 3A of continuous load current over a wide operating input voltage of 4.75V to 18V. Current mode control provides fast transient response and cycle-by-cycle current limit.An adjustable soft-start prevents inrush current at turn-on and in shutdown mode, the supply current drops below 1µA.The MP1484 is PIN compatible to the MP1482 2A/18V/Synchronous Step-Down Converter.FEATURES• 3A Continuous Output Current• Wide 4.75V to 18V Operating Input Range • Integrated 85m Ω Power MOSFET Switches • Output Adjustable from 0.925V to 15V • Up to 95% Efficiency • Programmable Soft-Start• Stable with Low ESR Ceramic Output Capacitors • Fixed 340KHz Frequency• Cycle-by-Cycle Over Current Protection • Input Under Voltage Lockout• Thermally Enhanced 8-Pin SOIC PackageAPPLICATIONS• FPGA, ASIC, DSP Power Supplies • LCD TV • Green Electronics/Appliances • Notebook Computers“MPS” and “The Future of Analog IC Technology” are Registered Trademarks of Monolithic Power Systems, Inc.TYPICAL APPLICATION10095908580757065605550E F F I C I E N C Y (%)0.11.010LOAD CURRENT (A)Efficiency vs Load CurrentPACKAGE REFERENCE* For Tape & Reel, add suffix –Z (e.g. MP1484EN -Z)For Lead Free, add suffix –LF (e.g. MP1484EN - LF-Z)ABSOLUTE MAXIMUM RATINGS (1)Supply Voltage V IN .......................–0.3V to +24V Switch Voltage V SW .................–1V to V IN + 0.3V Boost Voltage V BS ..........V SW – 0.3V to V SW + 6V All Other Pins.................................–0.3V to +6V Junction Temperature...............................150°C Lead Temperature....................................260°C Storage Temperature .............–65°C to +150°CRecommended Operating Conditions (2)Input Voltage V IN ............................4.75V to 18V Output Voltage V OUT ....................0.925V to 15V Ambient Operating Temp..............–20°C to +85°CThermal Resistance (3)θJA θJCSOIC8N(Exposed Pad)..........50......10...°C/WNotes:1) Exceeding these ratings may damage the device. 2) The device is not guaranteed to function outside of itsoperating conditions.3) Measured on approximately 1” square of 1 oz copper.ELECTRICAL CHARACTERISTICSV IN = 12V, T A= +25°C, unless otherwise noted.Parameter Symbol Condition Min Typ Max UnitsShutdown Supply Current V EN = 0V0.3 3.0 µA Supply Current V EN = 2.0V, V FB = 1.0V1.31.5mAFeedback VoltageV FB4.75V ≤ V IN ≤ 18V0.900 0.925 0.950 V Feedback Overvoltage Threshold 1.1 V Error Amplifier Voltage Gain (4) A EA 400 V/V Error Amplifier Transconductance G EA∆I C = ±10µA 820 µA/V High-Side/Low-Side Switch On-Resistance (4)85 m Ω High-Side Switch Leakage Current V EN = 0V, V SW = 0V 0 10 µA Upper Switch Current Limit Minimum Duty Cycle 3.8 5.3 A Lower Switch Current LimitFrom Drain to Source0.9 A COMP to Current Sense Transconductance G CS5.2A/VOscillation FrequencyF osc1300 340 380 KHzShort Circuit Oscillation Frequency F osc2 V FB = 0V 110 KHz Maximum Duty Cycle D MAX V FB = 1.0V 90 %Minimum On Time (4)T ON 220 ns EN Shutdown Threshold Voltage V EN Rising 1.1 1.5 2.0 V EN Shutdown Threshold Voltage Hysterisis220 mVELECTRICAL CHARACTERISTICS (continued) V IN = 12V, T A = +25°C, unless otherwise noted.Parameter Symbol Condition Min Typ Max UnitsEN Lockout Threshold Voltage2.2 2.5 2.7 V EN Lockout Hysterisis210 mV Input Under Voltage Lockout ThresholdV IN Rising3.804.054.40VInput Under Voltage Lockout Threshold Hysteresis 210 mVSoft-Start Current V SS = 0V 6 µA Soft-Start PeriodC SS = 0.1µF 15 ms Thermal Shutdown (4)160 °CNote:4) Guaranteed by design, not tested.PIN FUNCTIONSPin #Name Description1 BSHigh-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFETswitch. Connect a 0.01µF or greater capacitor from SW to BS to power the high side switch. 2 INPower Input. IN supplies the power to the IC, as well as the step-down converter switches.Drive IN with a 4.75V to 18V power source. See Input Capacitor .3 SW Power Switching Output. SW is the switching node that supplies power to the output. Connectthe output LC filter from SW to the output load. Note that a capacitor is required from SW toBS to power the high-side switch.4 GND Ground (Connect the exposed pad to Pin 4).5 FB Feedback Input. FB senses the output voltage and regulates it. Drive FB with a resistivevoltage divider connected to it from the output voltage. The feedback threshold is 0.925V. SeeSetting the Output Voltage .6 COMP Compensation Node. COMP is used to compensate the regulation control loop. Connect aseries RC network from COMP to GND. In some cases, an additional capacitor from COMP toGND is required. See Compensation Components.7 ENEnable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn onthe regulator; low to turn it off. Attach to IN with a 100k Ω pull up resistor for automatic startup.8 SS Soft-Start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GNDto set the soft-start period. A 0.1µF capacitor sets the soft-start period to 15ms. To disable thesoft-start feature, leave SS unconnected.MP1484TYPICAL PERFORMANCE CHARACTERISTICSC1 = 4.7µF, C2 = 2 x 10µF, L= 10µH, C SS= 0.1µF, T A = +25°C, unless otherwise noted.MP1484OPERATIONFUNCTIONAL DESCRIPTIONThe MP1484 regulates input voltages from 4.75V to 18V down to an output voltage as low as 0.925V, and supplies up to 3A of load current.The MP1484 uses current-mode control to regulate the output voltage. The output voltage is measured at FB through a resistive voltage divider and amplified through the internal transconductance error amplifier. The voltage at the COMP pin is compared to the switch current (measured internally) to control the output voltage.The converter uses internal N-Channel MOSFET switches to step-down the input voltage to the regulated output voltage. Since the high side MOSFET requires a gate voltage greater than the input voltage, a boost capacitor connected between SW and BS is needed to drive the high side gate. The boost capacitor is charged from the internal 5V rail when SW is low. When the FB pin voltage exceeds 20% of the nominal regulation value of 0.925V, the over voltage comparator is tripped and the COMP pin and the SS pin are discharged to GND, forcing the high-side switch off.ENCOMPSSFBGNDSWBSINFigure 1—Functional Block DiagramAPPLICATIONS INFORMATIONCOMPONENT SELECTIONSetting the Output VoltageThe output voltage is set using a resistive voltage divider connected from the output voltage to FB. The voltage divider divides the output voltage down to the feedback voltage by the ratio:2R 1R 2R V V OUTFB +=Thus the output voltage is:2R 2R 1R 925.0V OUT +×= R2 can be as high as 100k Ω, but a typical value is 10k Ω. Using the typical value for R2, R1 is determined by:)925.0V (81.101R OUT −×= (k Ω)For example, for a 3.3V output voltage, R2 is 10k Ω, and R1 is 26.1k Ω. Table 1 lists recommended resistance values of R1 and R2 for standard output voltages.Table 1—Recommended Resistance ValuesVOUT R1 R2 1.8V 9.53k Ω 10k Ω 2.5V 16.9k Ω 10k Ω 3.3V 26.1k Ω 10k Ω 5V 44.2k Ω 10k Ω 12V 121k Ω 10k ΩInductorThe inductor is required to supply constant current to the load while being driven by the switched input voltage. A larger value inductor will result in less ripple current that will in turn result in lower output ripple voltage. However, the larger value inductor will have a larger physical size, higher series resistance, and/or lower saturation current. A good rule for determining inductance is to allow the peak-to-peak ripple current to be approximately 30% of the maximum switch current limit. Also, make sure that the peak inductor current is below the maximum switch current limit.The inductance value can be calculated by:⎟⎟⎠⎞⎜⎜⎝⎛−×∆×=IN OUT L S OUTV V 1I f V L Where V OUT is the output voltage, V IN is the input voltage, f S is the switching frequency, and ∆I L is the peak-to-peak inductor ripple current. Choose an inductor that will not saturate under the maximum inductor peak current, calculated by:⎟⎟⎠⎞⎜⎜⎝⎛−×××+=IN OUT S OUT LOAD LP V V 1L f 2V I I Where I LOAD is the load current.The choice of which style inductor to use mainly depends on the price vs. size requirements and any EMI constraints.Optional Schottky DiodeDuring the transition between the high-side switch and low-side switch, the body diode of the low-side power MOSFET conducts the inductor current. The forward voltage of this body diode is high. An optional Schottky diode may be paralleled between the SW pin and GND pin to improve overall efficiency. Table 2 lists example Schottky diodes and their Manufacturers.Table 2—Diode Selection GuidePart NumberVoltage/CurrentRatingVendorB130 30V, 1A Diodes, Inc. SK1330V, 1ADiodes, Inc. MBRS130 30V, 1AInternationalRectifierInput CapacitorThe input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the AC current while maintaining the DC input voltage. Use low ESR capacitors for the best performance. Ceramic capacitors are preferred, but tantalum or low-ESR electrolytic capacitors will also suffice.Choose X5R or X7R dielectrics when using ceramic capacitors.Since the input capacitor (C1) absorbs the input switching current, it requires an adequate ripple current rating. The RMS current in the input capacitor can be estimated by:⎟⎟⎠⎞⎜⎜⎝⎛×−×=IN OUT IN OUT LOAD 1C V V1V V I I The worst-case condition occurs at V IN = 2V OUT , where I C1 = I LOAD /2. For simplification, use an input capacitor with a RMS current rating greater than half of the maximum load current. The input capacitor can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor, i.e. 0.1µF, should be placed as close to the IC as possible. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at input. The input voltage ripple for low ESR capacitors can be estimated by:⎟⎟⎠⎞⎜⎜⎝⎛−×××=∆IN OUT IN OUT S LOAD IN V V 1V V f 1C I V Where C1 is the input capacitance value.Output CapacitorThe output capacitor (C2) is required to maintain the DC output voltage. Ceramic, tantalum, or low ESR electrolytic capacitors are recommended. Under typical application conditions ， a minimum ceramic capacitor value of 20 µF is recommended on the output. Low ESR capacitors are preferred to keep the output voltage ripple low. The output voltage ripple can be estimated by:⎟⎟⎠⎞⎜⎜⎝⎛××+×⎟⎟⎠⎞⎜⎜⎝⎛−××=∆2C f 81R V V 1L f V V S ESR IN OUT S OUT OUTWhere C2 is the output capacitance value and R ESR is the equivalent series resistance (ESR) value of the output capacitor.When using ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance which is the main cause for the output voltage ripple. For simplification, the output voltage ripple can be estimated by:⎟⎟⎠⎞⎜⎜⎝⎛−××××=IN OUT 2SOUTOUT V V 12C L f 8V ∆V When using tantalum or electrolytic capacitors,the ESR dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated to:ESR IN OUT S OUT OUT R V V 1L f V ∆V ×⎟⎟⎠⎞⎜⎜⎝⎛−××=The characteristics of the output capacitor also affect the stability of the regulation system. The MP1484 can be optimized for a wide range of capacitance and ESR values.Compensation ComponentsMP1484 employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the COMP pin. COMP is the output of the internal transconductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to govern the characteristics of the control system. The DC gain of the voltage feedback loop is given by:OUTFB EA CS LOAD VDC V V A G R A ×××=Where V FB is the feedback voltage (0.925V),A VEA is the error amplifier voltage gain, G CS is the current sense transconductance and R LOAD is the load resistor value.The system has two poles of importance. One is due to the compensation capacitor (C3) and the output resistor of the error amplifier, and the other is due to the output capacitor and the load resistor. These poles are located at:VEA EA1P A 3C 2G f ××π=LOAD2P R 2C 21f ××π=Where G EA is the error amplifier transconductance.The system has one zero of importance, due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at:3R 3C 21f 1Z ××π=The system may have another zero of importance, if the output capacitor has a large capacitance and/or a high ESR value. The zero, due to the ESR and capacitance of the output capacitor, is located at:ESRESR R 2C 21f ××π=In this case, a third pole set by thecompensation capacitor (C6) and the compensation resistor (R3) is used to compensate the effect of the ESR zero on the loop gain. This pole is located at:3R 6C 21f 3P ××π=The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency where the feedback loop has the unity gain is important. Lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system instability. A good standard is to set the crossover frequency below one-tenth of the switching frequency.To optimize the compensation components, the following procedure can be used.1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine R3 by the following equation:FBOUTCS EA S FB OUT CS EA C V V G G f 1.02C 2V V G G f 2C 23R ×××××π<××××π=Where f C is the desired crossover frequency which is typically below one tenth of the switching frequency.2. Choose the compensation capacitor (C3) to achieve the desired phase margin. For applications with typical inductor values, setting the compensation zero (f Z1) below one-forth of the crossover frequency provides sufficient phase margin.Determine C3 by the following equation:Cf 3R 243C ××π>Where R3 is the compensation resistor.3. Determine if the second compensation capacitor (C6) is required. It is required if the ESR zero of the output capacitor is located at less than half of the switching frequency, or the following relationship is valid:2f R 2C 21S ESR <××πIf this is the case, then add the secondcompensation capacitor (C6) to set the pole f P3 at the location of the ESR zero. Determine C6 by the equation:3R R 2C 6C ESR×=External Bootstrap DiodeAn external bootstrap diode may enhance the efficiency of the regulator, the applicable conditions of external BS diode are:z V OUT is 5V or 3.3V; andzDuty cycle is high: D=INOUTV V >65% In these cases, an external BS diode is recommended from the output of the voltage regulator to BS pin, as shown in Fig.2Diode to Enhance EfficiencyThe recommended external BS diode is IN4148, and the BS cap is 0.1~1µF.TYPICAL APPLICATION CIRCUITFigure 3—MP1484 with 3.3V Output, 2X10µF Ceramic Output CapacitorPCB LAYOUT GUIDEPCB layout is very important to achieve stable operation. It is highly recommended to duplicate EVB layout for optimum performance.If change is necessary, please follow these guidelines and take Figure4 for reference. 1) Keep the path of switching current short and minimize the loop area formed by Input cap, high-side MOSFET and low-side MOSFET.2) Bypass ceramic capacitors are suggestedto be put close to the Vin Pin.3) Ensure all feedback connections are shortand direct. Place the feedback resistors and compensation components as close to the chip as possible.4) Rout SW away from sensitive analog areassuch as FB.5) Connect IN, SW, and especially GNDrespectively to a large copper area to cool the chip to improve thermal performance and long-term reliability.INPUT 4.75V to 23VOUTPUTC5Figure 4—MP1484 Typical Application Circuit and PCB Layout GuideMP1484。
24G15N 用户手册说明书
24G15N安全 (1)标志惯例 (1)电源 (2)安装 (3)清洁 (4)其它 (5)设置 (6)物品清单 (6)安装支架和底座 (7)调整视角 (8)连接显示器 (9)Adaptive-Sync功能 (10)HDR (11)调节显示器 (12)热键 (12)OSD设定 (13)Luminance（明亮度） (14)Color Setup（颜色设置） (15)Picture Boost（窗口增亮） (16)OSD Setup（OSD设置） (17)Game Setting（游戏设置） (18)Extra（其它） (19)Exit（退出） (20)LED指示灯 (21)故障排除 (22)规格 (23)主要规格 (23)预设显示模式 (24)引脚分配 (25)即插即用版权说明.................................................................................................................................................................. ..................................................................................................................................................................2626安全标志惯例以下小节描述此文档中使用的标志惯例。
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注意：“注意”表示潜在的硬件损坏或数据丢失，并告诉您如何避免出现问题。
EZ1584I资料
R2 232 Ohm, 1%
R2 VOUT = VREF • 1 + + I ADJ • R 2 R1
EZ1584C & EZ1584I
POWER MANAGEMENT Absolute Maximum Ratings
7.0 Amp Low Dropout Positive Voltage Regulators
Features
K Low dropout performance: 1.3V max. for EZ1584C K Full current rating over line and temperature K Fast transient response K ±2% total output regulation over line, load and K K K K K K K K K K K K K K
TJ TSTG TLEAD ESD
°C °C °C kV
Electrical Characteristics
Unless otherwise specified: Adj. VIN = 2.75V to 7.0V and Adj. IO = 10mA to 7.0A; Fixed VIN = 4.75 to 7.0V and Fixed IO = 0 mA to 7.0A. Values in bold apply over full operating ambient temperature range.
Pin Descriptions
Pin 1 Pin Name ADJUST Pin Function This pin is the negative side of the reference voltage for adjustable devices. Transient response can be improved by adding a small bypass capacitor from the adjust pin to ground. This pin is the bottom end of the internal resistor feedback chain for fixed output voltage parts, and should be connected to ground. This is the power output of the device and is electrically connected to the TAB. This is the input supply pin for both the control circuitry and the pass device.
mp1584中文资料_数据手册_参数
MP1584
3A, 1.5MHz, 28V Step-Down Converter
FEATURES
Wide 4.5V to 28V Operating Input Range Programmable Switching Frequency from
100kHz to 1.5MHz High-Efficiency Pulse Skipping Mode for
Symbol Condition
Min
Feedback Voltage Upper Switch On Resistance Upper Switch Leakage Current Limit COMP to Current Sense Transconductance Error Amp Voltage Gain (5) Error Amp Transconductance Error Amp Min Source current Error Amp Min Sink current VIN UVLO Threshold VIN UVLO Hysteresis Soft-Start Time (5) Oscillator Frequency Shutdown Supply Current Quiescent Supply Current Thermal Shutdown
Thermal Shutdown Hysteresis Minimum Off Time (5) Minimum On Time (5)
EN Up Threshold
EN Hysteresis
1.35
Note: 5) Guaranteed by design.
Typ 0.8 150 1 4.7
LT1585CM-3.3中文资料
θJA = 50°C/W
VIN
LT1584CT-3.3 LT1584CT-3.45 LT1585CT-3.3 LT1585CT-3.45
VOUT LT1587CT-3.3 LT1587CT-3.45
GND LT1584CT-3.38 LT1584CT-3.6
LT1584: C2 = 22µF, LT1585/LT1587: C2 = 10µF
1585 TA01
NOTE: MICROPROCESSOR APPLICATIONS WITH LOAD TRANSIENTS OF 3.8A REQUIRE
OUTPUT DECOUPLING CAPACITANCE > 1300µF ON FIXED VOLTAGE PARTS TO ACHIEVE < 50mV OF DEVIATION FROM NOMINAL OUTPUT. CONSULT FACTORY FOR DETAILS
q 1.225 (– 2%) 1.250 1.275 (+ 2%)
V
Output Voltage
LT1584-3.3 LT1585-3.3
LT1587-3.3
4.75V ≤ VIN ≤ 6.3V, 0mA ≤ IOUT ≤ 7A 4.75V ≤ VIN ≤ 7V, 0mA ≤ IOUT ≤ 4.6A, TJ ≥ 25°C 4.75V ≤ VIN ≤ 7V, 0mA ≤ IOUT ≤ 4A, TJ < 25°C 4.75V ≤ VIN ≤ 7V, 0mA ≤ IOUT ≤ 3A
M PACKAGE
T PACKAGE
3-LEAD PLASTIC DD PAK
viper28L
VIPER28低待机功率开关电源转换器原理与应用收藏 | 分类: | 查看: 52 | 评论(0)摘要：VIPER28是ST公司生产的一种集PWM控制器和800V高压功率MOSFET于同一芯片上的离线转换器，待机功率低于50mW，适用于机顶盒、DVD播放机、录音机开关电源和低/*率适配器以及ATX、消费类与家用设备的辅助电源和LED照明电源。
1、概述意法半导体（ST）公司推出的离线（off-line）高压变换器系列IC又增加了一个新的成员——VIPER28。
这种新型器件是一种将800V 功率MOSFET和高性能低压PWM控制器组合在一起的IC。
VIPER28其它功能和电路主要有两电平过电流保护、过电压和过载保护、滞后热保护、软启动和故障解除之后的自动重新启动。
突发（burst）模式操作和非常低的功率消耗满足待机（standby）节能规范。
先进的频率抖动可以降低电磁干扰（EMI）滤波器的成本。
高压启动电路已嵌入到芯片上。
VIPER28的工作频率有60KHz（VIPER28LN）和115KHz （VIPER28HN）两种。
2、VIPER28的基本结构和引脚功能VIPER28主要由高性能低压PWM控制器和带电流感测的高压MOSFET两个部分组成，芯片电路组成如图1所示。
VIPER28的控制器电路包含带频率颤抖特性的振荡器、带软启动特征的启动电路、PWM逻辑、带可调设定点的电流限制电路、第二过电流保护电路、突发模式管理电路、额外电源管理（EPT）电路、欠电压锁定（UVLO）电路、自动重新启动电路和热保护电路等。
栅极驱动器驱动一个BV DSS≥800V、RDS（on）=7Ω（在25℃时）的N沟道功率MOSFET。
这种集成MOSFET由于带有各种无损耗电流感测特性，故被称为“SenseFET”。
VIPER28采用7引脚双列直插式（DIP）封装，外形与引脚排列如图2所示。
VIPER28的各个引脚功能见表1。
3、主要性能与特点VIPER28的主要性能与特点有：（1）集低压PWM控制器与800V的SenseFET与同一芯片上，仅需外加少量元件，即可构建高性能的宽范围AC输入的反激式离线转换器。