Harmonic Tuning Antennas Using Slots and Short-pins

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SYSTEM AND METHOD FOR TUNING MIMO ANTENNAS

专利名称：SYSTEM AND METHOD FOR TUNING MIMOANTENNAS发明人：Osama Nafeth Saleem Alrabadi,KevinBoyle,Marian Madan申请号：US14710218申请日：20150512公开号：US20160337872A1公开日：20161117专利内容由知识产权出版社提供专利附图：摘要：This disclosure provides a device and method for tuning multiple-in multiple-out (MIMO) antennas. The method can include determining a plurality of subbandspectral efficiency values related to the MIMO antennas. The method can also include determining a wideband spectral efficiency by averaging the plurality of subband spectral efficiency values. The method can also include filtering the wideband spectral efficiency using an infinite impulse response (IIR) filter to determine an IIR filtered wideband spectral efficiency. The method can also include determining a cost function based on a maximum value of the IIR filtered wideband spectral efficiency. The method can also include tuning the MIMO antennas based at least in part on the cost function.申请人：QUALCOMM Incorporated地址：San Diego CA US国籍：US更多信息请下载全文后查看。

ANSYS 网络分析器 MS4661A E 和 MS4662A 产品说明说明书

1913T est port output characteristicsAperture frequency fixed mode (GPDL Y): delay range (DRG); 40 ns to 400 ms (1-2-4 sequence, aperture frequency = 0.4/DRG)Aperture frequency free mode (GPDL Y): 1 Hz (correspond to 400 ms) to 400 MHz (correspond to 1 ns)–High-speed mode (HSDL Y): τ = ∆θ/(360 x aperture frequency)[∆θ: phase measurement range, aperture frequency = SPAN x smoothing aperture (%). Smoothing aperture can be set between 20 to 2/MEP x 100 (%).]2.78 x 10–5/aperture frequency, DRG/14400 when set by DRG Phase measurement dynamic accuracy/(360 x aperture frequency)T est port level (input)10 to 0 dB0 to –40 dB –40 to –50 dB –50 to –60 dB –60 to –70 dB –70 to –80 dB –80 to –90 dB±6.0˚≤1.0 GHz Measurement accuracy ±0.3˚±0.3˚±0.8˚±2.0˚±6.0˚±20˚±6.0˚>1.0 GHz ±0.3˚±0.8˚±2.0˚±6.0˚±20˚–Test port level (input)+10 to 0 dB0 to –40 dB –40 to –50 dB –50 to –60 dB –60 to –70 dB –70 to –80 dB –80 to –90 dB±0.30 dB ≤1.0 GHz Measurement accuracy ±0.05 dB ±0.05 dB ±0.10 dB ±0.30 dB ±1.20 dB ±4.00 dB±0.30 dB >1.0 GHz ±0.05 dB ±0.10 dB ±0.30 dB ±1.20 dB ±4.00 dB–Measurement accuracyCompared to –10 dBm at test port level, RBW: 10 Hz)Dynamic accuracyMeasurement range Display resolutionDynamic accuracy±180˚(resolution: 0.001˚)0.01˚/div to 50˚/div (1-2-5 sequence)Measurement accuracyCompared to –10 dBm at test port level, RBW: 10 Hz)Frequency 100 to 500 kHz 500 kHz to 2 GHz 2 to 3 GHzDeviation –0.5 to +2.5 dB –1.5 to +1.5 dB –2.0 to +2.0 dBFrequency 100 to 500 kHz 500 kHz to 2 GHz 2 to 3 GHzDeviation –0.5 to +2.5 dB –1.5 to +1.5 dB –2.0 to +2.0 dBGPC-7+20 dBm, DC ±40 V (AC couple)<–90 dBm (100 kHz to 80 MHz, RBW: 1 kHz)<–80 dBm (80 MHz to 3 GHz, RBW: 1 kHz)0 dB, 20 dB (switching error: ±1 dB)Range: –70 to +10 dBmAccuracy: ≤±1.0 dB (100 MHz, 0 dBm)Linearity: ≤±0.5 dB (–10 to +8 dBm, compared to100 MHz/0 dBm)Resolution: 0.01 dBOutput level deviation: Compared to 100 MHz/0 dBmSignal purity T est port connector Frequency RBWMaximum input levelAverage noise levelCrosstalkMeasurement range Display resolutionSSB phase noise (offset frequency: 10 kHz):–90 dBc/Hz (100 kHz to 80 MHz), –85 dBc/Hz (80 MHz to 1 GHz), –80 dBc/Hz (1 to 3 GHz)Non-harmonic spurious: ≤–30 dBc (output level: 0 dBm)Harmonic distortion: ≤–25 dBc (output level: 0 dBm)N-J100 kHz to 3 GHz0 dBm (DC couple)Measurement of transmission characteristics (S 21, TB): <–90 dBm (100 kHz to 80 MHz, RBW: 1 kHz), <–80 dBm (80 MHz to 3 GHz, RBW: 1 kHz)Measurement of reflection characteristics (S 11, TA): <–70 dBm (100 kHz to 80 MHz, RBW: 1 kHz), <–60 dBm (80 MHz to 3 GHz, RBW: 1 kHz)–>90 dB (100 kHz to 1 GHz)*, >80 dB (1 to 3 GHz)**Improved to >105 dB by calibration≥100 dB (resolution: 0.001 dB)0.01 dB/div to 50 dB/div (1-2-5 sequence)Range: –10 to +10 dBmAccuracy: ≤±1.0 dB (100 MHz, 0 dBm)Linearity: ≤±0.5 dB (–10 to +10dBm, compared to100 MHz/0 dBm)Resolution: 0.01 dBOutput level deviation: Compared to 100 MHz/0 dBmImpedanceOutput level50 ΩT est port input characteristicsMagnitude measurementPhasemeasurementGroup delay measurementT est port attenuator Measurement rangeResolution Dynamic accuracy3 Hz to 10 kHz (1-3 sequence), AUTO (auto-setting with sweep time)Continued on next page192ModelMS4661A/EMS4662A>30 dB (300 kHz to 3 GHz), >22 dB (100 to 300 kHz)>15 dB (300 kHz to 1.5 GHz)>10 dB (100 kHz to 3 GHz)>10 dB (300 kHz to 1.5 GHz)>8 dB (100 kHz to 3 GHz)>25 dB (300 kHz to 1.5 GHz)>22 dB (100 kHz to 3 GHz)>15 dB (300 kHz to 1.5 GHz)>10 dB (100 kHz to 3 GHz)<2 dB (300 kHz to 80 MHz), <5 dB (100 kHz to 3 GHz)<2 dB (300 kHz to 80 MHz), <5 dB (100 kHz to 3 GHz)>90 dB (100 kHz to 1 GHz), >80 dB (1 to 3 GHz)EMC *1Impulse/step responseFrequency response, 1-port OSL, 1-pass 2-ports Frequency response, 1-port OSL, full 2-ports, 1-path 2-ports MS4661A: 640 x 400 dots, 8.9” color LCD MS4661E: 640 x 400 dots, 8.9” EL 640 x 400 dots, 8.9” color LCDInput waveform analysis FilteringTime domain range Range resolution Windows GatingFrequency sweep Level sweep Sweep timeNumber of measuring pointsSweep function Multi-marker Frequency markerMarker function Target data searchDisplayCalculation Auto-scale Time displayTDmeasurementSweepMarkerCalibration method Reference plane extendDisplayHard copy Data storageMeasurement data memory Internal computerAuxiliary input and outputPowerDimensions and mass Operating temperature range SafetyEN55011: 1991, Group 1, Class A EN50082-1: 1992Band pass (LOG/LIN MAG, PHASE, REAL, IMAG), low pass (LOG/LIN MAG, PHASE, REAL, IMAG)(numbers of measuring points in frequency domain –1)[ns]Frequency span width (GHz)Time span/(number of measuring points – 1)RECT ANGULAR, NOMINAL, LOW SIDELOBE, MIN SIDELOBEFrequency response of specified range measurable after gate specification in time-domain LIN: CENTER/SPAN, START/STOP , LOG: START/STOP LIN: START/STOP/STEP10 ms to 27.5 h (differs with measurement items, number of measuring points, RBW, display condition)11, 21, 51, 101, 251, 501, 1001 points (display: 501 points)Sweep range: Full, part, listed-frequencySweep control: REPEAT, SINGLE, STOP/CONTUp to 10 independent markers set for each trace (independent/linked setting possible)Marker position settable at frequencyNORMAL MKR, ∆MKR, 0 MKR, MKR →MAX, MKR →MIN, MKR →CF , ∆MKR →SPAN, MKR →OFFSET, MKR → +PEAK, MKR → –PEAK, MKR TRACK +PEAK, MKR TRACK –PEAKOFF , MIN, MAX, P-P , MEAN, σ, 1st +PEAK, 1st –PEAK, NEXT +PEAK, NEXT –PEAK, 1 dB COMP , XdB BW, XdB FREQ, Ripple 1, Ripple 2, Ripple 3, Ripple 4Electrical length can be corrected.Range: 0 to ±999999.9999999 m, Resolution: 100 nm Complex number input/output of (+, –, x, ÷), SUM, DIFF , conjugate complex number operationA/B trace independently settableY ear, month, date, time (display and settable)Video plotter: Hard copy at video plotter using separate video output Direct plot: Hard copy at printer or plotter (HP-GL, GP-GL) via GPIBFollowing data saved to or recalled from PMC or floppy disk (external FDD required): Measurement condition/calibration data (max. 10 items), PTA application programFollowing measurement data saved as display and complex data in same memory as measurement setup, etc.:T race A memory (XMA), trace B memory (XMB), trace A sub-memory (SMA), trace B sub-memory (SMB)PTAReference oscillator input: 10 MHz ±10 Hz, TTL level, BNC-J connector Reference oscillator buffer output: 10 MHz, TTL level, BNC-J connector GPIB: meets IEEE-488 (24-pole connector)I/O ports: PTA-αparallel input/output Module bus: for external module controlVideo output: separate video output (DIN-type, 8-pole), digital RBG output (Dsub-type, 9-pole)85 to 132 Vac/170 to 250 Vac, ≤220 VA 426 (W) x 222 (H) x 450 (D) mm, ≤24 kg 0˚ to 50˚CDirectivity *1Source match Load matchTransmission frequency response Reflection frequency response Crosstalk*1: Electromagnetic CompatibilityTest port characteristics•Test port characteristics (pre-calibration)*1: 23˚ to 35˚CEN61010-1: 1993 (Installation Category ΙΙ, Pollution Degree ΙΙ)1933Model/Order ModelConnector Directivity Source match Load matchT ransmission frequency response Reflection frequency response CrosstalkMS4661A/E *3MS4662A Main frameMS4661A Network Analyzer (color LCD, built-in bridge)MS4661E Network Analyzer (EL display, built-in bridge)MS4662A Network Analyzer (color LCD, built-in S-parameter)Standard accessories E001Power cord, 2.5 m:1 pc J0266Adapter (3 poles to2 poles conversion plug): 1 pc F0014Fuse, 6.3 A:1 pc F0043Fuse, 1 A (MS4662A only):2 pcs Z0280A List band (MS4662A only):1 pc W0996AE MS4661A/E operation manual (MS4661A/E only):1 copy W0997AE MS4662A operation manual (MS4662A only): 1 copy W0998AE GPIB operation manual: 1 copy W0999AE PTA operation manual:1 copyOptionMS4661/4662-01High stability reference oscillator (aging rate: ≤±2 x 10–8/day)Optional accessories3750SMA/3.5 mm calibration kit (open, short, termination, 7 mm-3.5 adapter)37517 mm calibration kit (open, short, termination)375350 Ω, N-type calibration kit (open, short, termination, 7 mm-N adapter)3753-7575 Ω, N-type calibration kit (open, short, termination, N-N adapter)J0629T est port cable (GPC-7 at both ends, 60 cm)J0729A Test port cable (N-M at both ends, 60 cm)J0730A Test port cable (3.5 mm-M at both ends, 60 cm)34AS50Adapter (GPC-7•WSMA-M)34ASF50Adapter (GPC-7•WSMA-F)34AN50Adapter (GPC-7•N-M)34ANF50Adapter (GPC-7•N-F)1091-26Adapter (N-M•SMA-M)1091-27Adapter (N-M•SMA-F)1091-80Adapter (N-F•SMA-M)1091-81Adapter (N-F•SMA-F)K220Adapter (K-M•K-M, SMA compatible)K222Adapter (K-F•K-F , SMA compatible)K224Adapter (K-M•K-F , SMA compatible)12N75B Matching pad (50 Ω→ 75 Ω, N-M•N-M)P0005Memory card (32 KB SRAM)P0006Memory card (64 KB SRAM)P0007Memory card (128 KB SRAM)P0008Memory card (256 KB SRAM)P0009Memory card (512 KB SRAM)MC3305A JIS Type PTA Keyboard MC3306A ASCII Type PTA Keyboard J0007GPIB cable, 1 m J0008GPIB cable, 2 mB0329D Front cover (1MW 5U)B0333D Rack mount kitB0334D Carrying case (hard type)Peripheral instruments VP870Printer (GPIB, EPSON)•Test port characteristics (typical values after 2-port OSL calibration *2)N >38 dB >35 dB>25 dB (300 kHz to 1.5 GHz)>22 dB (100 kHz to 3 GHz)±0.02 dB ±0.02 dB >105 dB3.5 mm (SMA)>38 dB >35 dB >35 dB ±0.02 dB ±0.02 dB >105 dB*2: T ypical values are for reference, they are not guaranteed.*3: 1-pass 2-port calibration Ordering informationPlease specify model/order number, name, and quantity when ordering.。

Shure Axient Digital 无线电系统说明书

Axient® Digital Wireless SystemsAXIENT®DIGITAL WIRELESS SYSTEMSIncorporating the most innovative wireless audio technology in the world, AxientDigital was engineered from the ground up for professional productions thatdemand flawless execution.With an unprecedented level of signal stability and audio clarity, plus flexiblehardware options, advanced connectivity, and comprehensive control, it’s awireless system built to take on the challenges of today—and tomorrow.RF PROTECTIONWith outstanding signal quality in even the most complex, congested environments, Axient®Digital ensures maximum stability, range, and clarity for uncompromisingaudio—anywhere, every time.AUDIO QUALITYAxient® Digital defies limitations for both RF and audio quality. With industry-leading low latency,transparent frequency response, and wide dynamic range, nothing gets in the way of true, puresound. No matter the setting, it’s Shure audio quality you can count on.COMMAND & CONTROLShowLink® remote control, Wireless Workbench®, the ShurePlus™ Channels app, andnetworked battery monitoring provide unmatched control and insight, for seamless performance. HARDWARE & SCALABILTYWith two transmitter series to choose from—both compatible with a shared receiver platform—Axient Digital is a scalable wireless system that provides incomparable sound for a wide range ofSystem SpecificationsRF Carrier Range470–960 MHzNote: Varies by region (See Frequency Range and Ouput Power table)Working Range100 m (330 ft)Note: Actual range depends on RF signal absorption, reflection and interference. RF Tuning Step Size25 kHz, varies by regionImage Rejection>70 dB, typicalRF Sensitivity−98 dBm at 10-5 BERLatency Standard mode: 2.0 ms High Density mode: 2.9 msAudio Frequency Response AD1: 20 Hz – 20 kHz (±1 dB) AD2: 20 Hz – 20 kHz (±1 dB) Note: Dependent on microphone typeAudio Dynamic RangeA-weighted, typical, System Gain @ +10XLR Analog Output: 120 dB (A-weighted); 117 (unweighted) Dante Digital Output: 130 dB (A-weighted); 126 (unweighted)Total Harmonic Distortion−6 dBFS input, 1 kHz, System Gain @ +10<0.01%System Audio Polarity Positive pressure on microphone diaphragm produces positive voltage on pin 2 (with respect to pin 3 of XLR output) and the tip of the 6.35 mm (1/4-inch) output.Operating Temperature Range−18 °C (0 °F) to 50 °C (122 °F)Note: Battery characteristics may limit this range.Storage Temperature Range−29 °C (−20 °F) to 65 °C (149 °F)Note: Battery characteristics may limit this range.Frequency RangeBand Range (MHz)Transmitter Output (mW)G53470 to 5102/10/35G54479 to 5652/10/20G55470 to 636*2/10/35G56470 to 6362/10/35G57470 to 616*2/10/35G62510 to 5302/10/35H54520 to 6362/10/35K53606 to 698*2/10/35K54606 to 663**2/10/35K55606 to 6942/10/35K56606 to 7142/10/35 K57606 to 7902/10/35 K58622 to 6982/10/35 L54630 to 7872/10/35 R52794 to 8062/10/35 JB806 to 8102/10X51925 to 937.52/10X55941 to 9602/10/35 Note: Not all frequencies available in all regions. Contact your authorized Shure dealer for availability.* with a gap between 608 to 614 MHz** with a gap between 608 to 614 MHz and a gap between 616 to 653 MHz Furnished AccessoriesReceivers90XN1371Hardware Kit95A8994BNC Bulkhead AdapterVar. by region½ Wave Receiver Antenna (2)95B9023BNC-BNC Cable (short)95C9023BNC-BNC Cable (long)95N2035Coaxial RF Cascade CableVar. by region AC Power Cable, VLockVar. by region AC Power Jumper Cable95A33402Ethernet Cable, 3 ft.95B33402Ethernet Jumper CableHandheld Systems95B2313Zipper Bag31B1856Euro-threaded Adapter90F4046Swivel Adapter, black80B8201AA Alkaline Batteries (2)Bodypack Systems80B8201AA Alkaline Batteries (2)Var. by region¼ Wave AntennaWA340Threaded TA4F AdapterWA610Transmitter Carrying Case26A13Zipper Bag44A12547Belt Clip NOTE:This Radio equipment is intended for use in musical professional entertainment and similar applications. This Radio apparatus may be capable of operating on some frequencies not authorized in your region. Please contact your national authority to obtain information on authorized frequencies and RF power levels for wireless microphone products. Rechargeable Power Management (sold separately)SB900A Rechargeable BatteryAD series transmitters are compatible with the SB900A lithium-ionrechargeable battery, which provides over 11 hours of continuous useand precise tracking of remaining life and charge cycle details.SBC200 Dual Docking Recharging StationThis compact and portable unit charges batteries while in transmittersor out. Up to 4 SBC200s can be chained together to run off one powersupply.SBC800 Eight Battery Recharging StationThis compact and portable unit charges up to 8 SB900A batteries tofull capacity within 3 hours, with status LEDs to indicate power levels.SB900A batteries fit securely in the charger for easy, efficient storageand transport.Battery Runtimes (Note: Frequency Band Dependent)Battery Type10 mWSB900A>11 hoursAlkaline8 hoursNiMH<11 hoursLi-primary<14 hoursOverviewThe AD4Q Axient Digital Quad Receiver sets a new standard in transparent digital audio and maximum spectral efficiency. Groundbreaking performance features include wide tuning, low latency, High Density (HD) mode, and Quadversity™, ensuring solid performance in the most challenging RF environments. Networked control, AES3 + Dante output, and signal routing options bring a new level of management and flexibility to your entire workflow. Compatible with all Axient Digital transmitters.Features• Wide tuning range up to 184MHz• True digital diversity reception per channel for drop-out resistance• Networked control with Wireless Workbench ® and ShurePlus ™ Channels app• Quadversity ™ mode for extended antenna coverage and improved RF signal-to-noise • Front panel headphone jack enables Dante Cue and Dante Browse monitoring • Configurable Ethernet switch for redundant Dante digital output • Switchable XLR/AES3 outputs• Channel Quality meter displays RF signal-to-noise • Locking AC connectors•Optional DC module available to support redundant powerSpecificationsDimensions 44 mm × 483 mm × 333 mm (1.7 in. × 19.0 in. × 13.1 in.), H × W × D Weight 4.8 kg (10.6 lbs), without antennas HousingSteel; Extruded aluminumPower Requirements 100 to 240 V AC, 50–60 Hz; 0.68 A max.Thermal Dissipation Maximum: 31 W (106 BTU/hr) Idle: 21 W (72 BTU/hr)Audio Output Gain Adjustment Range –18 to +42 dB in 1 dB steps (plus Mute setting)Configuration 1/4" (6.35 mm): T ransformer-coupled Balanced (T ip=audio, Ring=no audio, Sleeve=ground)XLR: T ransformer-coupled Balanced (1=ground, 2=audio +, 3=audio -)ImpedanceT ypical, XLR Line out100ΩFull Scale Output 200 k Ω load 1/4" (6.35 mm): +8 dBVXLR: LINE setting= +18 dBV , MIC setting= –12 dBV Mic/Line Switch30 dB pad Phantom Power Protection YesNetworking Network Interface10/100 Mbps, 1 Gbps, Dante Digital Audio Network Addressing Capability DHCP or Manual IP address Maximum Ethernet Cable Length 100 m (328 ft)Cascade output Connector T ype BNCNote: For connection of one additional receiver in the same bandConfiguration Unbalanced, passive Impedance 50 ΩInsertion Loss 0 dB, typicalRF Input Spurious Rejection >80 dB, typical Connector T ype BNC Impedance 50 ΩBias Voltage12–13.5 V DC, 150 mA maximum, per antenna, switchable on/off RF Carrier Frequency RangeModel-dependentAD4Q=A: 470–636 MHz AD4Q=B: 606–810 MHz AD4Q=C: 750–960 MHzAD4Q Four-Channel Receiver Front PanelAD4Q Four-Channel Receiver Rear PanelOverviewThe AD4D Axient Digital Dual Receiver sets a new standard in transparent digital audio and maximum spectral efficiency. Groundbreaking performance features include wide tuning, low latency, and High Density (HD) mode, ensuring solid performance in the most challenging RF environments. Networked control and signal routing options bring a new level of management and flexibility to your entire workflow. Compatible with all Axient Digital transmitters.Features• Wide tuning range up to 184MHz• True digital diversity reception per channel for drop-out resistance• Networked control with Wireless Workbench ® and ShurePlus ™ Channels app • Front panel headphone jack enables Dante Cue and Dante Browse monitoring • Configurable Ethernet switch for redundant Dante digital output • AES3 output• Channel Quality meter displays RF signal-to-noise • Locking AC connectors•Optional DC module available to support redundant powerSpecificationsDimensions 44 mm × 483 mm × 333 mm (1.7 in. × 19.0 in. × 13.1 in.), H × W × D Weight 4.6 kg (10.1 lbs), without antennas HousingSteel; Extruded aluminumPower Requirements 100 to 240 V AC, 50–60 Hz; 0.26 A max.Thermal Dissipation Maximum: 23 W (78 BTU/hr) Idle: 15 W (52 BTU/hr)Audio Output Gain Adjustment Range –18 to +42 dB in 1 dB steps (plus Mute setting)Configuration 1/4" (6.35 mm): T ransformer-coupled Balanced (T ip=audio, Ring=no audio, Sleeve=ground)XLR: T ransformer-coupled Balanced (1=ground, 2=audio +, 3=audio -)ImpedanceT ypical, XLR Line out100ΩFull Scale Output 200 k Ω load 1/4" (6.35 mm): +8 dBVXLR: LINE setting= +18 dBV , MIC setting= –12 dBV Mic/Line Switch30 dB pad Phantom Power Protection YesNetworking Network Interface10/100 Mbps, 1 Gbps, Dante Digital Audio Network Addressing Capability DHCP or Manual IP address Maximum Ethernet Cable Length 100 m (328 ft)Cascade output Connector T ype BNCNote: For connection of one additional receiver in the same bandConfiguration Unbalanced, passive Impedance 50 ΩInsertion Loss 0 dB, typicalRF Input Spurious Rejection >80 dB, typical Connector T ype BNC Impedance 50 ΩBias Voltage12–13.5 V DC, 150 mA maximum, per antenna, switchable on/off RF Carrier Frequency RangeModel-dependentAD4D=A: 470–636 MHz AD4D=B: 606–810 MHz AD4D=C: 750–960 MHzAD4D Dual-Channel Receiver Front PanelAD4D Dual-Channel Receiver Rear PanelOverviewAD series bodypack transmitters deliver impeccable audio quality and RF performance with wide-tuning, High Density (HD) mode, and encryption. Features durable metal construction, AA or SB900A rechargeable power (with dockable charging), and TA4 or LEMO3 connector options.Features• Two transmission modes:- Standard for optimal coverage- New High Density mode for maximum system channel count and robust coverage• Encryption-enabled, secure transmission• External contacts for docked charging• AA or SB900A Li-ion rechargeable batteries• Detachable ¼ wave antenna• LEMO3 and TA4 connector optionsSpecificationsGain Offset Range–12 to 21 dB (in 1 dB steps)Battery T ype Shure SB900A Rechargeable Li-Ion or LR6 AA batteries 1.5 VBattery Runtime @ 10 mW Shure SB900A: up to 9 hours Alkaline: up to 8 hoursSee Battery Runtime ChartDimensions86 mm × 66 mm × 23 mm (3.4 in. × 2.6 in. × 0.9 in.) H × W × D Weight142 g (5.0 oz.), without batteriesHousing Cast AluminumAudio InputConnectorSee drawing for details 4-Pin male mini connector (TA4M) LEM03 connectorConfiguration Unbalanced ImpedanceSee drawing for details1 MΩMaximum Input Level 1 kHz at 1% THD Pad Off: 8.5 dBV (7.5 Vpp) Pad On: 20.5 dBV (30 Vpp)Preamplifier Equivalent Input Noise (EIN)System Gain Setting ≥ +20120 dBV, A-weighted, typicalRF OutputConnector SMAAntenna T ype1/4 waveImpedance50 ΩOccupied Bandwidth<200 kHzModulation T ype Shure Axient Digital ProprietaryPower 2 mW, 10 mW, 35 mWSee Frequency Range and Ouput Power table, varies by region Microphone Options (see catalog for more)WL93WL93condenser capsule, omnidirectional lavalier micWL183 WL183condenser capsule, omnidirectional lavalier micWL184WL184condenser capsule, supercardioid lavalier micWL185WL185condenser capsule, cardioid lavalier micMX150-C MX150 condenser capsule, cardioid lavalier micMX150-O MX150 condenser capsule, omnidirectional lavalier micMX153MX153 condenser capsule, omnidirectional earset headworn mic SM35SM35 condenser capsule, cardioid headset micWBH53WBH53condenser capsule, omnidirectional headworn mic WBH54WBH54condenser capsule, supercardioid headworn micWB98H/CWB98H/C condenser capsule, cardioid instrument clip micAD1 Bodypack TransmitterOverviewAD series hand-held transmitters deliver impeccable audio quality and RF performance with wide-tuning, High Density (HD) mode, and encryption. Features durable metal construction, AA or SB900A rechargeable power (with dockable charging), and black or nickel finish options.Features• Two transmission modes:- Standard for optimal coverage- New High Density mode for maximum system channel count and robust coverage• Encryption-enabled, secure transmission• Frequency and power lockout• Rugged metal construction in black or nickel finish• External contacts for docked charging• AA or SB900A Li-ion rechargeable batteries• Backlit LCD with easy-to-navigate menu and controls• Low-profile, lockable power switch• Available cartridges: KSM8, KSM9HS, Beta® 87A/87C, Beta® 58, SM58®, VP68SpecificationsMic Offset Range–12 to 21 dB (in 3 dB steps)Battery T ype Shure SB900A Rechargeable Li-Ion or LR6 AA batteries 1.5 VBattery Runtime @ 10 mW Shure SB900A: >11 hours Alkaline: 8 hoursSee Battery Runtime ChartDimensions256 mm × 51 mm (10.1 in. × 2.0 in.) L × D Weight340 g (12.0 oz.), without batteries Housing Cast aluminumAudio InputConfiguration UnbalancedMaximum Input Level 1 kHz at 1% THD,145 dB SPL, typical (SM58) Note: dependent on microphone typeRF OutputAntenna T ype Integrated Single-Band HelicalOccupied Bandwidth<200 kHzModulation T ype Shure Axient Digital ProprietaryPower 2 mW, 10 mW, 35 mWSee Frequency Range and Ouput Power table, varies by regionMicrophone Options (see catalog for more)RPW112SM58® Cardioid Dynamic Vocal Wireless Microphone CapsuleRPW118Beta® 58A Supercardioid Dynamic Vocal Wireless Microphone CapsuleRPW120Beta® 87A Supercardioid Condenser Vocal Wireless Microphone CapsuleRPW122Beta® 87C Cardioid Condenser Vocal Wireless Microphone CapsuleRPW124VP68 Omnidirectional Condenser Wireless Microphone CapsuleRPW170KSM8 Dualdyne™ Cardioid Dynamic Wireless Microphone Capsule (Nickel)RPW174KSM8 Dualdyne™ Cardioid Dynamic Wireless Microphone Capsule (Black)RPW184KSM9 Dual-Pattern Condenser Wireless Microphone Capsule (Black)RPW186KSM9HS Multi-Pattern Dual Diaphragm Condenser Wireless Microphone Capsule (Black)RPW188KSM9 Dual-Pattern Condenser Wireless Microphone Capsule (Nickel)RPW190KSM9HS Multi-Pattern Dual Diaphragm Condenser Wireless Microphone Capsule (Nickel)AD2 Handheld Transmitter。

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⽂献翻译英⽂论⽂翻译天线性能⽬录PROPERTIES OF ANTENNAS (2)2.1 ANTENNA RADIATION (3)2.2 GAIN (5)2.3 EFFECTIVE AREA (8)2.4 PATH LOSS (9)2.5 RADAR RANGE EQUATION AND CROSS SECTION (11)2.6 WHY USE AN ANTENNA? (14)天线的功能 (14)2.1天线辐射 (15)2.2 天线增益 (17)2.3天线有效⾯积..................................... 错误！未定义书签。

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英⽂原⽂：PROPERTIES OF ANTENNASOne approach to an antenna book starts with a discussion of how antennas radiate. Beginning with Maxwell’s equations, we derive electromagnetic waves. After that lengthy discussion, which contains a lot of mathematics, we discuss how these waves excite currents on conductors. The second half of the story is that currents radiate and produce electromagnetic waves. You may already have studied that subject, or if you wish to further your background, consult books on electromagnetics.The study of electromagnetics gives insight into the mathematics describing antenna radiation and provides the rigor to prevent mistakes. We skip the discussion of those equations and move directly to practical aspects.It is important to realize that antennas radiate from currents. Design consists of controlling currents to produce the desired radiation distribution, called its pattern .In many situations the problem is how to prevent radiation from currents, such as in circuits. Whenever a current becomes separated in distance from its return current, it radiates. Simply stated, we design to keep the two currents close together, to reduce radiation. Some discussions will ignore the current distribution and instead, consider derived quantities, such as fields in an aperture or magnetic currents in a slot or around the edges of a microstrip patch. You will discover that we use any concept that provides insight or simplifies the mathematics.An antenna converts bound circuit fields into propagating electromagnetic waves and, by reciprocity, collects power from passing electromagnetic waves. Maxwell’s equations predict that any time-varying electric or magnetic field produces the opposite field and forms an electromagnetic wave. The wave has its two fields oriented orthogonally, and it propagates in the direction normal to the plane defined by the perpendicular electric and magnetic fields. The electric field, the magnetic field, and the direction of propagation form a right-handed coordinate system. Thepropagating wave field intensity decreases by 1/R away from the source, whereas a static field drops off by 1/2R . Any circuit with time-varying fields has the capability of radiating to some extent.We consider only time-harmonic fields and use phasor notation with time dependence jwt e . An outward-propagating wave is given by ()j kR wt e --, where k, the wave number, is given by 2π/λ. λ is the wavelength of the wave given by c/f , where c is the velocity of light (3 ×810 m/s in free space) and f is the frequency. Increasing the distance from the source decreases thephase of the wave.Consider a two-wire transmission line with fields bound to it. The currents on a single wire will radiate, but as long as the ground return path is near, its radiation will nearly c ancel the other line’s radiation because the two are 180°out of phase and the waves travel about the same distance. As the lines become farther and farther apart, in terms of wavelengths, the fields produced by the two currents will no longer cancel in all directions. In some directions the phase delay is different for radiation from the current on each line, and power escapes from the line. We keep circuits from radiating by providing close ground returns. Hence, high-speed logic requires ground planes to reduce radiation and its unwanted crosstalk.2.1 ANTENNA RADIATIONAntennas radiate spherical waves that propagate in the radial direction for a coordinate system centered on the antenna. At large distances, spherical waves can be approximated by plane waves. Plane waves are useful because they simplify the problem. They are not physical, however, because they require infinite power.The Poynting vector describes both the direction of propagation and the power density of the electromagnetic wave. It is found from the vector cross product of the electric and magnetic fields and is denoted S:S = E ×H* W/2mRoot mean square (RMS) values are used to express the magnitude of the fields. H* is the complex conjugate of the magnetic field phasor. The magnetic field isproportional to the electric field in the far field. The constant of proportion is η, the impedance of free space (η = 376.73Ω):2E S S η==W/2m(1.1)Because the Poynting vector is the vector product of the two fields, it is orthogonal to both fields and the triplet defines a right-handed coordinate system: (E, H, S).Consider a pair of concentric spheres centered on the antenna. The fields around the antenna decrease as 1/R, 1/2R , 1/3R , and so on. Constant-order terms would require that the power radiated grow with distance and power would not be conserved. For field terms proportional to 1/2R , 1/3R , and higher, the power density decreases with distance faster than the area increases. The energy on the inner sphere is larger than that on the outer sphere. The energies are not radiated but are instead concentrated around the antenna; they are near-field terms. Only the 1/2R term of the Poynting vector (1/R field terms) represents radiated power because the sphere area grows as 2R and gives a constant product. All the radiated power flowing through the inner sphere will propagate to the outer sphere. The sign of the input reactance depends on the near-field predominance of field type: electric (capacitive) or magnetic (inductive). At resonance (zero reactance) the stored energies due to the near fields are equal. Increasing the stored fields increases the circuit Q and narrows the impedance bandwidth. Far from the antenna we consider only the radiated fields and power density. The power flow is the same through concentric spheres:2211,22,44avg avg R S R S ππ= The average power density is proportional to 1/2R . Consider differential areas on the two spheres at the same coordinate angles. The antenna radiates only in the radial direction; therefore, no power may travel in the θ or φ direction. Power travels in flux tubes between areas, and it follows that not only the average Poynting vector but alsoevery part of the power density is proportional to 1/2R :221122sin sin S R d d S R d d θθφθθφ=Since in a radiated wave S is proportional to 1/2R , E is proportional to 1/R. It is convenient to define radiation intensity to remove the 1/2R dependence:U(θ, φ) = S(R, θ, φ) 2R W/solid angleRadiation intensity depends only on the direction of radiation and remains the same at all distances. A probe antenna measures the relative radiation intensity (pattern) by moving in a circle (constant R) around the antenna. Often, of course, the antenna rotates and the probe is stationary.Some patterns have established names. Patterns along constant angles of the spherical coordinates are called either conical (constant θ) or great circle (constant φ). The great circle cuts when φ = 0 °or φ = 90°are the principal plane patterns. Othernamed cuts are also used, but their names depend on the particular measurement positioner, and it is necessary to annotate these patterns carefully to avoid confusion between people measuring patterns on different positioners. Patterns are measured by using three scales: (1) linear (power), (2) square root (field intensity), and (3) decibels (dB). The dB scale is used the most because it reveals more of the low-level responses (sidelobes).Figure 1.1 demonstrates many characteristics of patterns. The half-power beamwidth is sometimes called just the beamwidth. The tenth-power and null beamwidths are used in some applications. This pattern comes from a parabolic reflector whose feed is moved off the axis. The vestigial lobe occurs when the first sidelobe becomes joined to the main beam and forms a shoulder. For a feed located on the axis of the parabola, the first sidelobes are equal.2.2 GAINGain is a measure of the ability of the antenna to direct the input power into radiation in a particular direction and is measured at the peak radiation intensity. Consider thepower density radiated by an isotropic antenna with input power Po at a distance R: S = Po/4π2R . An isotropic antenna radiates equally in all directions, and its radiated power density S is found by dividing the radiated power by the area of the sphere 4π2R . The isotropic radiator is considered to be 100% efficient. The gain of an actual antenna increases the power density in the direction of the peak radiation:2024E PG S R πη== or 014PG E S R ηηπ== (1.2) Gain is achieved by directing the radiation away from other parts of the radiation sphere. In general, gain is defined as the gain-biased pattern of the antenna:()()02,,4P G S R θφθφπ= power density ()()0,,4P G U θφθφπ= radiation intensity(1.3)FIGURE 1.1 Antenna pattern characteristics.The surface integral of the radiation intensity over the radiation sphere divided by the input power Po is a measure of the relative power radiated by the antenna, or the antenna efficiency:()2000,sin 4r e G P d d P ππθφθθφηπ==?? efficiency where Pr is the radiated power. Material losses in the antenna or reflected power due to poor impedance match reduce the radiated power. In this book, integrals in the equation above and those that follow express concepts more than operations we perform during design. Only for theoretical simplifications of the real world can we find closed-form solutions that would call for actual integration. We solve most integrals by using numerical methods that involve breaking the integrand into small segments and performing a weighted sum. However, it is helpful that integrals using measured values reduce the random errors by averaging, which improves the result. In a system the transmitter output impedance or the receiver input impedance may not match the antenna input impedance. Peak gain occurs for a receiver impedance conjugate matched to the antenna, which means that the resistive parts are the same and the reactive parts are the same magnitude but have opposite signs. Precision gain measurements require a tuner between the antenna and receiver to conjugate-match the two. Alternatively, the mismatch loss must be removed by calculation after the measurement. Either the effect of mismatches is considered separately for a given system, or the antennas are measured into the system impedance and mismatch loss is considered to be part of the efficiency.Example Compute the peak power density at 10 km of an antenna with an input power of 3 W and a gain of 15 dB.First convert dB gain to a ratio: G = 151010 = 31.62. The power spreads over the sphere area with radius 10 km or an area of 4π42(10) 2m . The power density is ()2823(31.62)75.5/410W S nW m m π==? We calculate the electric field intensity using Eq. (1-2):()()975.510376.75333/E S V m ηµ-==?= Although gain is usually relative to an isotropic antenna, some antenna gains are referred to a λ/2 dipole with an isotropic gain of 2.14 dB.If we approximate the antenna as a point source, we compute the electric field radiated by using Eq. (1.2):()()0,,4j k R PG e E R θφηθφπ-= (1.4)This requires only that the antenna be small compared to the radial distance R. Equation (1.4) ignores the direction of the electric field, which we define as polarization. The units of the electric field are volts/meter. We determine the far-field pattern by multiplying Eq. (1.4) by R and removing the phase term jkR e - since phase has meaning only when referred to another point in the far field. The far-field electric field ff E unit is volts:()()0,,4ff PG E θφηθφπ= or ()()2014,,ff G E P πθφθφη??= (1.5) During analysis, we often normalize input power to 1 W and can compute gain easily from the electric field by multiplying by a constant 4πη = 0.1826374.1.3 EFFECTIVE AREAAntennas capture power from passing waves and deliver some of it to the terminals. Given the power density of the incident wave and the effective area of the antenna, the power delivered to the terminals is the product.d e f f P S A = (1.6)For an aperture antenna such as a horn, parabolic reflector, or flat-plate array, effective area is physical area multiplied by aperture efficiency. In general, losses dueto material, distribution, and mismatch reduce the ratio of the effective area to the physical area. Typical estimated aperture efficiency for a parabolic reflector is 55%. Even antennas with infinitesimal physical areas, such as dipoles, have effective areas because they remove power from passing waves.2.4 PATH LOSSWe combine the gain of the transmitting antenna with the effective area of the receiving antenna to determine delivered power and path loss. The power density at the receiving antenna is given by Eq. (1.3), and the received power is given by Eq. (1.6). By combining the two, we obtain the path loss:()212,4d t A G P P R θφπ= Antenna 1 transmits, and antenna 2 receives. If the materials in the antennas are linear and isotropic, the transmitting and receiving patterns are identical (reciprocal) [2, p. 116]. When we consider antenna 2 as the transmitting antenna and antenna 1 as the receiving antenna, the path loss is()122,4d t AG P P Rθφπ= Since the responses are reciprocal, the path losses are equal and we can gather and eliminate terms:1212G G A A == constant Because the antennas were arbitrary, this quotient must equal a constant. This constant was found by considering the radiation between two large apertures [3]:24G A πλ= (1.7)We substitute this equation into path loss to express it in terms of the gains or effective areas:21212224d t P A A G G P R R λπλ??==(1.8)We make quick evaluations of path loss for various units of distance R and for frequency f in megahertz using the formula. pathloss(dB)=()()()1220log U K fR G dB G dB +--(1.9)where Ku depends on the length units:Example Compute the gain of a 3-m-diameter parabolic reflector at 4 GHz assuming 55% aperture efficiency.Gain is related to effective area by Eq. (1.7):24AG πλ=We calculate the area of a circular aperture by ()2/2A D π=. By combining theseequations, we have22a a D Df G c ππηηλ== ? ?(1.10)where D is the diameter and a η is the aperture efficiency. On substituting the values above, we obtain the gain:()()29934100.5586850.310G π== (39.4dB)Example Calculate the path loss of a 50-km communication link at 2.2 GHz using a transmitter antenna with a gain of 25 dB and a receiver antenna with a gain of 20 dB.Path loss = 32.45 + 20 log[2200(50)] - 25 - 20 = 88.3 dBWhat happens to transmission between two apertures as the frequency is increased? If we assume that the effective area remains constant, as in a parabolic reflector, the transmission increases as the square of frequency:2212122221d t P A A A A f Bf P R R c λ??===where B is a constant for a fixed range. The receiving aperture captures the same power regardless of frequency, but the gain of the transmitting antenna increases as the square of frequency. Hence, the received power also increases as frequency squared. Only for antennas, whose gain is a fixed value when frequency changes, does the path loss increase as the square of frequency. 2.5 RADAR RANGE EQUATION AND CROSS SECTIONRadar operates using a double path loss. The radar transmitting antenna radiates a field that illuminates a target. These incident fields excite surface currents that also radiate to produce a second field. These fields propagate to the receiving antenna, where they are collected. Most radars use the same antenna both to transmit the field and to collect the signal returned, called a monostatic system, whereas we use separate antennas for bistatic radar. The receiving system cannot be detected in a bistatic system because it does not transmit and has greater survivability in a military application.We determine the power density illuminating the target at a range T R by usingEq. (1.2):()2,4T T inc TP G S R θφπ=(1.11)The target’s radar cross section (RCS), the scattering area of the object, is expressed in square meters or dB 2m : 10log(square meters). The RCS depends on both the incident and reflected wave directions. We multiply the power collected by the target with its receiving pattern by the gain of the effective antenna due to the currents induced:()2,,,4r e f l e c t e d s r r i i T T T p o w e r P R C S p o w e r d e n s i t y i n c i d e n t P G R θφθφσπ=== (1.12)In a communication system we call Ps the equivalent isotropic radiated power (EIRP), which equals the product of the input power and the antenna gain. The target becomes the transmitting source and we apply Eq. (1.2) to find the power density at the receiving antenna at a range R R from the target. Finally, the receiving antenna collects the power density with an effective area R A . We combine these ideas to obtain the power delivered to the receiver:()()()22,,,44R T T r r i i rec R R T R A P G P S A R R σθφθφππ==We apply Eq. (1.7) to eliminate the effective area of the receiving antenna and gather terms to determine the bistatic radar range equation:()()2322,,,4T R r r i i rec TT R G G P P R R λσθφθφπ= (1.13)We reduce Eq. (1.13) and collect terms for monostatic radar, where the same antenna is used for both transmitting and receiving:()22344rec T P G P Rλσπ= Radar received power is proportional to 1/4R and to 2G .We find the approximate RCS of a flat plate by considering the plate as an antenna with an effective area. Equation (1.11) gives the power density incident onthe plate that collects this power over an area R A :()2,4T T C R TP G P A R σθφπ= The power scattered by the plate is the power collected,C P , times the gain of the plateas an antenna,P G :()()2,,4T T i i s C P R P r rT P G P P G A G R θφθφπ== This scattered power is the effective radiated power in a particular direction, which in an antenna is the product of the input power and the gain in a particular direction. We calculate the plate gain by using the effective area and find the scattered power in terms of area:22244T T R s T P G A P R ππλ= We determine the RCS σ by Eq. (1.12), the scattered power divided by the incident power density:()()2222,,444R i i R r r s R T T T G G P A P G R θφθφλπσπλπ=== (1.14)The right expression of Eq. (1.14) divides the gain into two pieces for bistatic scattering, where the scattered direction is different from the incident direction. Monostatic scattering uses the same incident and reflected directions. We can substitute any object for the flat plate and use the idea of an effective area and its associated antenna gain. An antenna is an object with a unique RCS characteristic because part of the power received will be delivered to the antenna terminals. If we provide a good impedance match to this signal, it will not reradiate and the RCS is reduced. When we illuminate an antenna from an arbitrary direction, some of the incident power density will be scattered by the structure and not delivered to the antenna terminals. This leads to the division of antenna RCS into the antenna mode ofreradiated signals caused by terminal mismatch and the structural mode, the fields reflected off the structure for incident power density not delivered to the terminals.2.6 WHY USE AN ANTENNA?We use antennas to transfer signals when no other way is possible, such as communication with a missile or over rugged mountain terrain. Cables are expensive and take a long time to install. Are there times when we would use antennas over level ground? The large path losses of antenna systems lead us to believe that cable runs are better.天线的性能⼀个⽅法是⼀本有关天线的书是从讨论天线如何辐射开始的。

一种新型的圆极化贴片天线的研究

2007年全国微波毫米波会议论文集308 一种新型的圆极化贴片天线的研究张继龙卢春兰钱祖平（解放军理工大学通信工程学院，江苏南京，210007）摘要：本文研究了圆极化微带贴片天线，通过在普通圆形贴片开槽，提出了一种结构新颖的圆极化贴片天线。

仿真以及实测结果表明，该天线具有较宽的3dB波瓣和良好的圆极化性能，并且新型贴片天线的尺寸要小于普通的圆形或圆环形贴片天线的尺寸。

关键词：贴片天线；圆极化；轴比A Novel Circular-polarized MicrostripPatch AntennaZhang Ji-long Lu Chun-lan Qian Zu-Ping（Communication Engineering Institute of Science Technology University PLA, jiangsu nanjing,21007）Abstract: In this paper a novel circular-polarized microstrip patch antenna is given based on the study of common circular microstrip patch antenna. This new type of patch looks like common circular patch with some slots. Numerical results and measured data indicate that the new patch antenna has a wide beam and good performance of axial ratio. The radiation pattern of the antenna is very good. Another property of the new patch antenna is that the size of new patch antenna is smaller than common circular patch or annular patch antenna.Key word: patch antenna; circular-polarization; axial ratio1 引言*微带贴片天线由于重量轻、体积小、剖面低，此外还具有良好的方向性、灵活的馈电方式且容易与其他印刷电路集成等优点，在许多领域有着广泛的应用前景。

2.45 GHz紧凑型微带整流天线阵列

DOI: 10.11991/yykj.202003012网络出版地址：https:///kcms/detail/23.1191.U.20201202.1409.012.html2.45 GHz 紧凑型微带整流天线阵列李金城，林航，刘长军四川大学电子信息学院，四川成都 610064摘要：为了提升整流天线的微波功率容量与直流输出功率，本文提出了一款基于肖特基二极管的紧凑型微带整流天线阵列，工作频率为2.45 GHz ，采用HSMS-2700肖特基二极管作为整流器件，并采用倍压电路提升功率容量与直流输出功率。

在输入微波功率2 W 时，单支整流电路的最大输出直流功率为0.93 W 。

将整流电路集成到贴片天线后，形成整流天线阵列。

结果表明，天线阵列最大可输出14.03 W 的直流功率，尺寸为217 mm×275 mm×2 mm 。

整流天线阵列结构紧凑，输出直流达到了117.6 mW/cm 3。

关键词：微波无线能量传输；整流天线；功率容量；直流输出；整流电路；肖特基二极管；倍压电路；天线阵列中图分类号：TN455 文献标志码：A 文章编号：1009−671X(2021)02−0008−04A compact microstrip rectenna array at 2.45 GHzLI Jincheng, LIN Hang, LIU ChangjunSchool of Electronics and Information Engineering, Sichuan University, Chengdu 610064, ChinaAbstract : In order to improve the power capacity and the DC output power of a rectenna, a compact microstrip rectifier rectenna array at 2.45 GHz based on Schottky diode was designed and fabricated. HSMS-2700 Schottky diodes are applied with voltage doubler rectifying circuit to improve its microwave power capacity and DC output power. When the input microwave power is 2 W, the maximum DC output power of a single rectifier reaches 0.93 W. The DC output power of the whole rectenna reaches 14.03 W at most. Its dimension is 217 mm×275 mm×2 mm. The proposed rectenna array iscompact, with DC output power reaching 117.6 mW/cm 3.Keywords: microwave wireless power transmission; rectenna; power capacity; DC output power; rectifier; Schottky diode; voltage doubler; antenna array随着不可再生能源的日益减少，可再生清洁能源的获取问题亟待解决。

AN_040_Folded_Dipole_Antenna_for_CC24XX_1_0(1)

Table of Contents1KEYWORDS (1)2INTRODUCTION (1)3ABBREVIATIONS (3)4DESIGN CRITERIA (4)5DESIGN DESCRIPTION (4)6SCHEMATICS AND LAYOUT (5)7TUNING (8)8TEST RESULTS (10)1.1.S UMMARY OF RESULTS (13)9CONCLUSION (13)10APPENDIX A - RADIATION DIAGRAMS (14)11GENERAL INFORMATION (26)1.2.D OCUMENT H ISTORY (26)1.3.D ISCLAIMER (26)1.4.T RADEMARKS (26)1.5.L IFE S UPPORT P OLICY (26)12ADDRESS INFORMATION (27)3 ABBREVIATIONSCurrentDirectDCBoardEvaluationEBEIRP Effective Isotropic Radiated PowerElectromagneticEMCC2400EM CC2400 Evaluation ModuleCommissionCommunicationsFCCFederalmaterialPCBCommonFR4KeyingShiftFrequencyFSKAmplifierNoiseLowLNAAmplifierPAPowerBoardCircuitPrintedPCBBandwidthResolutionRBWFrequencyRadioRFChokeFrequencyRadioRFCconnectorRFSMACommonDeviceRangeSRDShortBandwidthVBWVideo4 DESIGN CRITERIAThe following design criteria were important for the antenna design:•Optimum load impedance 115 + j180 Ohm, differential•DC-connection between RF pins and TXRX_switch pin•TXRX_switch pin isolated from RF• Few components• Manufacturability•Low spurious emission• Low losses• OmnidirectionalityThe optimum termination impedance is a trade-off between optimum source impedance for the internal LNA and optimum load for the internal PA. The TXRX_switch pin level is 0 V in receive mode to provide ground for the LNA and 1.8 V in transmit mode to provide the required supply voltage to the PA. This pin should be isolated from the RF signals by using a shunt capacitor and/or a series inductor (RFC).Antennas that are electrically short compared to the wavelength tend to be sensitive to component variations in the tuning network. Electrically small antennas may cause yield problems or require individual tuning.Pay special attention to the harmonic levels for operation in the 2.4 GHz SRD band. Both the second and third harmonic will fall within protected bands as defined by FCC part 15.In typical SRD applications, it is desired that the antenna radiates equally in all directions, i.e. that the antenna is omni directional.A folded dipole is attractive because of its high impedance that makes it easier to match to the optimum impedance for the CC2400. The theoretical impedance is 292 Ohm for a half wavelength folded dipole. A shunt inductor should provide the inductive part of the optimum load impedance while reducing the real part. The folded dipole is a metal loop that will provide DC contact between the RF pins. In addition the mid point of the antenna is virtual ground, meaning that a connection can be made to the TXRX switch pin without distorting antenna performance. The folded dipole is a resonant structure that should be less sensitive to component variations and provide low losses. The radiation pattern of a folded dipole is omni-directional in the plane normal to the antenna.5 DESIGN DESCRIPTIONAn initial investigation to check the feasibility of the design was performed using the Smith chart. Plotting the 292 Ohm in the Smith chart and adding a 15 nH shunt inductor resulted in 115 + j141 Ohm.The CC2400EM reference design was selected as the base for the design. The CC2400EM is a radio module with balun and an SMA connector. The balun with the SMA connector is designed to work with 50 Ohm unbalanced devices such as a ¼ wave antenna and most RF instrumentsThe antenna was implemented on the PCB as part of the layout. The antenna was placed relatively close to the CC2400 to keep the design compact.The antenna design was simulated before the layout was made. The antenna was designed using an EM simulator and the matching circuit was simulated using a linear simulator and S-parameters from the EM simulation.The first step in the simulation was to design a folded dipole on a FR4 PCB in front of a ground plane of the same size as the CC2400EM. The length of the antenna was adjusted until the impedance was 290 Ohm. The next step was to add feed lines with pads for a shunt inductor and a transmission line to the virtual ground point of the antenna for DC connection to the TXRX switch pin. The transmission line to the TXRX switch pin was connected to ground during the simulations and was fitted with pads for a series inductor. The inductor pads were defined as ports to make it easy to simulate with various inductors in the following S-parameter simulations. Due to the PCB material and the ground plane, the antenna became shorter than the theoretical half wavelength. Finally, the inductor values were determined using a linear simulator, S-parameters from the antenna simulation and S-parameters for the inductors.6 SCHEMATICS AND LAYOUTFigure 1 shows the schematic of the CC2400EM with the folded dipole antenna. Figure 2 shows the board layout. The distance to the antenna and extension of the ground plane behind the antenna are critical parameters. If the PCB is wider than the CC2400EM board, the ground plane, components and tracks should be pulled away from the end points of the antenna.7 TUNINGThe purpose of tuning is to maximise output power while maintaining good spectrum properties. Figure 3 shows the spectrum when CC2400 is configured to transmit continuously random data at 1 Mbps. It is measured with a cable between the spectrum analyser and the CC2400EM. The cable and the instrument is 50 Ohm and a good impedance match for the CC2400EM. Figure 3 also illustrates how to judge a good spectrum. The marker measures the difference between the peak power level and the first null. It should be at least 25 dB, typically 28 dB, for no degradation in transmission. The difference in frequency is 760 kHz. It is important to measure with 100 kHz RBW and a 100kHz VBW. It is also an advantage to apply averaging for the measurements over the air. (Note: The plot use different settings on RBW and VBW)Figure 3: Reference spectrum for CC2400 at 1 Mbps.Poor matching degrades the output spectrum as illustrated in Figure 4. This measurement is obtained using an antenna connected to the spectrum analyser. The CC2400EM is tested with no antenna connected to, i. e. the SMA connector left open. In this case the mismatch occurs due to the open circuit when the antenna is removed from the EM. Transmission is lost even at small distances because of spectrum degradation. The received level is adequate, but the FSK signal is too degraded to be demodulated.Figure 4: Example of poor spectrum, antenna removed from EM.The tuning set up is shown in Figure 5. It consists of a whip antenna mounted on a copper sheet and connected to a spectrum analyser. A copper sheet is not required; it was used to have a stable set-up. To achieve reliable measurements, the CC2400 EB onto which the CC2400 EM to be tested was mounted, was placed in three different positions on the copper sheet. The power received by the whip antenna was read in the three positions and the average was used for comparison of the different configurations. The tuning of the antenna was performed in a laboratory without absorbers or other features for antenna characterisation. It is important to average measurements as small changes in position could give significant changes in received levels due to reflections. The RBW was set to 2 MHz with a 3.8 MHz span and averaging was set to 50 when making power measurements. The spectrum was checked using an RBW = VBW = 100 kHz. The inductor values were stepped up and down and the average power level was recorded as well as the depth of the first nullsin the spectrum.Figure 6: EB with CC2400EM with whip antenna.Figure 7: EB with CC2400EM with folded dipole antenna.Whip, DK xy-planeWhip, DK xy-planeWhip, DK xz-planeWhip, DK xz-planeWhip, DK yz-planeWhip, DK yz-planeFolded dipole xy-planeFolded dipole xy-planeFolded dipole xz-planeFolded dipole xz-planeFolded dipole yz-planeFolded dipole yz-plane。

Polarization Agile Slot-Ring Array Antenna using Magic-T Circuit

Figure 2: Schematic electric fields of the slot-ring array antenna (a) the +45-deg. LP (b) the -45-deg. LP (c) the RHCP (d) the LHCP
3. Basic behavior of the array antenna
Figure 2 shows the schematic electric fields on the slot-ring array antenna. The slot-ring array antenna works with four behaviors according to the phase condition of the Magic-T. The RF signal transmits to the antenna elements through the feed circuit as shown in Fig. 2. In this array, the four-mode operations are achieved with very simple structure using a combination odd and even transmission mode on the feed circuit. When the RF signal from Port 4 is fed to the antenna elements through the feed circuit. The +45-deg. LP is excited as shown in Fig. 2 (a). In the same way, the -45-deg. LP is excited when the RF signal from Port 5 is fed (Fig. 2 (b)). It is possible to feed the antenna array with ± 90-deg. phase difference signals as well. When the phase of Port 5 is 90-deg. advanced to Port 4, the LHCP is excited. In the same way, the RHCP is excited when the phase of Port 4 is 90-deg. advanced to Port 5.

Design and Optimization of Wideband Hat-Fed Reflector Antenna

Thesis for the degree of Licentiate of EngineeringDesign and Optimization of Wideband Hat-Fed Reﬂector Antenna with Radome for Satellite Earth StationbyErik G.GeterudDepartment of Signals and SystemsChalmers University of TechnologyG¨o teborg,Sweden2012G¨o teborg2012Design and Optimization of Wideband Hat-Fed Reﬂector Antenna with Radome for Satellite Earth StationErik G.GeterudThis thesis has been prepared using L A T E X.Copyright c Erik G.Geterud,2012.All rights reserved.Department of Signals and SystemsTechnical Report No.R013/2012ISSN1403-266XDepartment of Signals and SystemsAntenna GroupChalmers University of TechnologySE-41296G¨o teborg,SwedenPhone:+46(0)317720000E-mail:erik.geterud@chalmers.sePrinted by Chalmers ReproserviceG¨o teborg,Sweden,September2012To my parentsAbstractThis thesis presents the development of a hat-fed reﬂector antenna with radome to be used as satellite earth station.The antenna with self sup-ported feed is relatively compact,circular symmetric and with low cross polarization.To achieve optimum performance over the satellite Ku-band, covering10.75-14.50GHz,a genetic algorithm optimization scheme was im-plemented and the simulations were done with the electromagnetic solver QuickWave-V2D based on the FDTD method.Optimizations were done to-wards minimized reﬂection coeﬃcient,maximized feed eﬃciency,andﬁnally taking into account the stringent sidelobe requirements deﬁned by the ETSI. Radomes for enclosing the satellite earth station have been analyzed and a low loss monolayer radome was manufactured and successfully measured with the hat-fed reﬂector antenna.The satellite earth station can after cer-tiﬁcation be operational.Keywords:Antenna feeds,corrugated surfaces,reﬂector antennas,opti-mization,radomes,satellite earth stations.iiiPrefaceThis thesis is in partial fulﬁllment for the degree of Licentiate of Engineering at Chalmers University of Technology.The work resulting in this thesis was done between April2008and Au-gust2012.I have during the licenciate period been an external industrial Ph.D.student fully employed by GlobalView Systems Sweden.The work has been done in close collaboration with the Antenna department at Arki-vator AB and the Antenna Group,in the Department of Signals and Systems, at Chalmers in G¨o teborg.Professor Per-Simon Kildal is the examiner and Associated Professor Jian Yang is the supervisor.iiiivList of PublicationsThis thesis is based on the work contained in the following papers:Paper IE.G.Geterud,Y.Yang and T.¨Ostling,“Wide band hat-fed reﬂector antenna for satellite communications”,in Proceedings of the5th European Conference on Antennas and Propagation,EUCAP2011,Rome,Italy,11-15April2011. Paper IIE.G.Geterud,Y.Yang and T.¨Ostling,“Radome design for hat-fed reﬂector antenna”,in Proceedings of the6th European Conference on Antennas and Propagation,EuCAP2012,Prague,Czech Republic,26-30March2012. Paper IIIE.G.Geterud,Y.Yang,T.¨Ostling and P.Bergmark,“Design and Opti-mization of a Compact Wideband Hat-Fed Reﬂector Antenna for Satellite Communications”,IEEE Transactions of Antennas and Propagation,to be published.Other related publications by the Author not included in this thesis:•E.G.Geterud,M.Hjelm,T.Ciamulski and M.Sypniewski“Simulation of a lens antenna using a parallelized version of an FDTD simulator”, in Proceedings of the3rd European Conference on Antennas and Prop-agation,EUCAP2009,Berlin,Germany,23-27March2009.vviAcknowledgementsFirst of all I would like to thank my examiner Professor Per-Simon Kildal, for accepting me as an industrial Ph.D.student in the Antenna group,and my supervisor Associated Professor Jian Yang.Both have been supportive and we had many fruitful technical discussions.Also,without the strong and long term support from GlobalView Systems including my colleague Matthew Wright my research at Chalmers could never have been realized.Thanks goes to Tomas¨Ostling at Arkivator for support with the GA opti-mization and hardware including the hat feed,reﬂector antenna and radome.I must also mention Dr Pontus Bergmark at Art and Technology for his craft-ing of radome prototypes and free-thinking spirit.Raul Timbus from Ruag Space has taken many Ph.D.courses with me and we had many enjoyable discussions on antennas and other topics.Thanks also to Marie Str¨o m in the Signal Processing group for keeping me in shape through lunch climbing sessions in Kopparbunken.I would like to thank all past and present members of the antenna group at Chalmers for creating an enjoyable working environment.The yearly ski trip arranged by Per-Simon has been an appreciated event with team building exercises and lots of fun.Also the whole department of Signals and Systems are acknowledged for creating a good atmosphere and arranging many en-joyable social events.ErikG¨o teborg,August2012viiContentsAbstract i Preface iii List of Publications v Acknowledgments vii Contents viii 1Introduction11.1Aim and Outline of the Thesis (3)2Antenna Technologies for Satellite Earth Stations52.1Reﬂector Antennas (5)2.2Antennas Feeds (7)2.2.1The Rear Radiating Cutler Feed (7)2.2.2Dual Mode Horn (8)2.3Array Antennas (8)2.4Earth Station Minimum Technical and Operational Require-ments (8)3QuickWave-V2D&Genetic Algorithm for Simulation and Optimization133.1QuickWave-V2D (13)3.2Optimization Methods Overview (14)3.3Genetic Algorithm (15)viii4The Hat Feed174.1Basic Concept of the Hat Feed (17)4.2Ring Focus (18)4.3Gaussian Vertex Plate (19)4.4Antenna Noise Temperature and G/T (20)4.5Characterization of the Hat Feed (20)4.5.1Eﬃciency (20)4.5.2Co-and Cross-Polar Radiation Patterns (22)4.5.3Reﬂection Coeﬃcient (22)5Radome255.1Background (25)5.2Monolayer Radome (26)5.3Sandwich Radome (27)5.4Radome Eﬀects on Antenna Performance (27)5.4.1Boresight Error (27)5.4.2Sidelobe Degradation (28)5.4.3Depolarization (28)5.4.4Voltage Standing Wave Ratio (29)5.4.5Insertion Loss (29)5.5Advances in Radome Development (29)5.5.1Metamaterials (29)5.5.2Frequency Selective Surfaces (29)6Optimization and Measurement of Hat-Fed Reﬂector An-tenna with Radome316.1Optimization (31)6.1.1Simulation Results (33)6.2Measurements (37)6.2.1Hat-Fed Reﬂector (37)6.2.2Radome with Hat-Fed Reﬂector (38)7Conclusions and Future Work477.1Conclusions (47)7.2Future Work (47)References49 Paper I:Wide Band Hat-Fed Reﬂector Antenna for Satellite Communications59 Abstract (59)ix1Introduction (59)2Hat feed optimization (59)3Gaussian vertex plate (61)4Measurement results (61)5Conclusions (62)Acknowledgment (62)References (62)Paper II:Radome design for hat-fed reﬂector antenna65 Abstract (65)1Introduction (65)2Radome design (65)3Measurements (65)4Conclusions (67)Acknowledgment (68)References (68)Paper III:Design and Optimization of a Compact Wideband Hat-Fed Reﬂector Antenna for Satellite Communications71 Abstract (71)1Introduction (71)2Characterization of hat feed for optimization (72)A Reﬂection Coeﬃcient (72)B Aperture Eﬃciency (72)C Co-and Cross-Polar Radiation Pattern (73)3Optimization of hat feed (73)4Gaussian Vertex Plate (75)5Reﬂector with ring-shaped focus (75)6Low cost monolayer radome (75)7Conclusions (78)References (78)xPart I Introductory chaptersChapter1IntroductionThe developed satellite earth station in this work is for communication with geosynchronous satellites and in thisﬁrst part a short introduction to the intriguing topic of satellite communication is given.The notion of a geosyn-chronous satellite for communication purposes wasﬁrst published in1928 (but not widely so)by the Austro-Hungarian rocket engineer and pioneer of cosmonautics Herman Potocnik(Noordung)[1].The idea of satellite commu-nication(satcom)was later made popular in1945by British scienceﬁction author,inventor,and futurist Arthur C.Clarke[2]but it was not until the launch of the Sputnik Satellite in1957that this idea was considered realistic. Theﬁrst communication satellite Telstar was launched in1962and since then numerous satellites have been launched with ever increasing sophistication.A communication satellite is a microwave repeater station that permits two or more users with appropriate earth stations to deliver or exchange infor-mation of various forms[3].The satellite is composed of three separate units being the fuel system,the satellite and telemetry controls and the transpon-der.The transponder includes antennas,receivers,input multiplexers,and a frequency converter which is used to reroute the received signals through a high powered ampliﬁer for downlink[3].The main task for a telecom satellite is to receive signals from earth stations and to relay them over a speciﬁc geo-graphical area deﬁned by the spotbeam of the transmitting satellite antenna. The communication link can be bi-directional as for satellite telephony etc. For Earth observation the satellite is equipped with cameras and sensors and downlinks the collected information.The Earth station may operate uplink in transmitting mode(Tx)and/or downlink in receiving mode(Rx).In case of uplink the transmitting station sends data in the form of baseband signals, which passes through a baseband processor,an up converter,a high powered ampliﬁer,and through the antenna to the satellite.The reverse process is1Chapter1.Introduction valid in receive mode.A scenario of satellite communications with various earth terminals is shown in Figure1.1.Figure1.1:Satellite communications scenario.The Geostationary Earth Orbit(GEO)refers to satellites that are placed in orbit such that they remain stationary relative to aﬁxed spot on earth. The satellites are placed at35,786km above the earth surface along the equa-tor,and its angular velocity is equal to that of the earth,thereby causing it to appear to be over the same point on earth.This allows for them to provide constant coverage of the area e.g.for television broadcasting.The distance from an earth station positioned at the equator to a geosynchronous satellite in zenith is35,786km which introduces a propagation delay of ap-proximately a quarter of a second when relaying a signal between two users on earth.Due to this time delay,bi-directional communications,are prefer-ably done via lower orbiting satellites.This is the case for omni-directional antennas and low data rates when no satellite tracking is required.Medium Earth orbit(MEO),sometimes called intermediate circular orbit (ICO),is the region of space around the Earth above low Earth orbit(al-titude of2,000km)and below geostationary orbit(altitude of35,786km). The orbital periods of MEO satellites range from about2-12hours and the dominating use is for positioning with GPS,Glonass and Galileo satellites.The Low Earth Orbit(LEO),refers to satellites in orbit160-2,000km above the earths surface which reduces transmission times.A LEO orbit21.1Aim and Outline of the Thesiscan also be used to cover a polar region,which the GEO cannot.Since the satellites do not appear stationary to earth stations the antenna may need to track the motion of the satellite.The most striking LEO satellite is arguably the International Space Station(ISS)which orbit varies from320-400km above the Earth’s surface.The main satellite communication bands being:•L-band,1-2GHz(GPS frequencies:1.575GHz L1,1.228GHz L2)•S-band,2-4GHz(Weather-and surface ship radar and ISS space shuttle telecom)•C-band,4-8GHz(Satcom bands:3.400-3.625GHz Rx,6.425-6.725Tx)•X-band,8-12GHz(Military radar and deep space telecom)•Ku-band,12-18GHz(Satcom bands:10.70-12.75GHz Rx,13.75-14.50 GHz Tx)•K-band,18-26.5GHz(Satcom band:17.70-20.20GHz Rx)•Ka-band,26.5-40GHz(Satcom band:27.50-30.00GHz Tx)In this thesis we present an earth station for communication with geo-stationary satellites in the form of a hat-fed reﬂector antenna with radome. The antenna design is for the Ku-satcom-band which cover a1.3:1bandwidth which is a challenging task in terms of reﬂection coeﬃcient and the stringent sidelobe requirements.The antenna and feed electronics needs to be enclosed by a radome to protect from harsh environment such as rain,snow,dust and wind.The radome must be low loss and designed in conjunction with the an-tenna to ensure satisfactory electromagnetic performance.Simulations and optimization techniques are used in order to fulﬁll the requirements on co-and cross-polar radiation patterns,reﬂection coeﬃcient and eﬃciency.1.1Aim and Outline of the ThesisThe aim of this thesis work is to develop and optimize a wideband hat-fed reﬂector antenna satellite earth station with radome.Previously,the hat feed has been used in terrestrial radio links and gauge radars etc.The bandwidth is narrow but encouraging work has been done towards wideband solutions [4].In this work we need to extend the bandwidth further by implement-ing optimization schemes in conjunction with an electromagnetic solver.If3Chapter1.Introduction successful it will be theﬁrst hat-fed reﬂector antenna used for satcom appli-cations[5,6]and a more compact solution than other reﬂector conﬁgurations available on the market.The radome is a critical component in the satellite earth station and it must be robust and low loss[7].This thesis is separated in two main parts.Theﬁrst part introduces the sub-ject and is divided as follows:Chapter2provides an overview of available antenna technologies for satellite communications and the selected topology is motivated.Chapter3introduces the electromagnetic solver used and the optimization technique.Chapter4presents the hat feed and its characteris-tics with Gaussian vertex plate,Antenna Noise Temperature and G/T factor. Chapter5introduces radomes including evaluation of monolayer-and sand-wich structures.Chapter6includes a description of the development work done and summarizes the appended papers.Chapter7ends theﬁrst part of the thesis with conclusions and future work.In the second main part,the contributions from the author are included as three appended papers.4Chapter2Antenna Technologies for Satellite Earth Stations2.1Reﬂector AntennasReﬂector antennas for microwaves evolved from the attempts to increase the directivity of half wave dipoles using sheet reﬂectors[8].Reﬂector anten-nas are today the most used antenna technology for satellite earth stations due to its simplicity and reliability and various types of directive feed horns have replaced the dipole feed except for some lower frequency applications. Reﬂector antennas can be grouped into:1.Prime focus reﬂectors[9]2.Oﬀset reﬂectors[9]3.Dual reﬂectors[9]•Splash plate[8]•Hat[10,11]•Cassegrainian[12]•Gregorian[12]•Displaced axis[13]The prime focus reﬂector is the most basic antenna conﬁguration and the advantages being simplicity in manufacturing and pointing.On the negative side the blockage from the feed and support struts will cause diﬀraction and scattering which aﬀects the radiation patterns and reﬂection coeﬃcient.5Chapter2.Antenna Technologies for Satellite Earth Stations The obvious advantage with the oﬀset conﬁguration is that blockage and scattering from the feed and struts are excluded.On the down side the radiation patterns will not be symmetrical and pointing and target tracking will become somewhat more complicated.The Green Bank radio telescope is the worlds largest steerable radio telescope and a grand example of an oﬀset reﬂector antenna,Figure2.1.Figure2.1:Large oﬀset reﬂector antenna(The Green Bank telescope in West Virginia).Image courtesy of NRAO/AUI[14].Dual reﬂector antennas oﬀer an additional degree of freedom in the sec-ondary reﬂector.These group of antennas may be of oﬀset-or center fed conﬁguration such as the hat feed which diﬀers from traditional dual re-ﬂectors which were originally designed through ray tracing methods in the optical region.The hat feed operates through mode coupling in the nearﬁeld region and this is examined in Chapter4.The secondary reﬂector will cause blockage if center fed so classical dual reﬂector antennas are only competitive for antennas that is large in terms of wavelengths(typically≥50λ).The nearﬁeld mode coupling of the hat feed allows a very small hat diameter (typically∼2λ)[6].62.2Antennas Feeds2.2Antennas FeedsThe most common way to feed a reﬂector antenna is by using a corrugatedhorn[15].This is a rather compact feed that generate nearly equal E-andH-plane radiation patterns with low cross polarization as a result.Widebanddesigns of1.5:1or more has been developed.For narrowﬂare angle feedsthe directivity of the feed can be high,e.g.for dual reﬂector systems,butthere will be frequency dispersion i.e.the phase center position of the feedwill change with frequency.Examples of wideband feeds are:•Quad ridge horn[15]•Vivaldi antenna[16]•Log periodic horns[17]The Eleven antenna[18]developed at Chalmers is an example of a logperiodic horn and its wideband performance and stable phase center makes ita suitable feed for radio astronomy[19,20,21].Other feed types to mentionare hard horns[22]which can be made compact and dipole feeds[16]forlower frequencies.2.2.1The Rear Radiating Cutler FeedA pioneer in the design of reﬂector antennas and feeds for microwaves wasC.C.Cutler from Bell Laboratories.An excellent introduction for the un-derstanding of reﬂector antennas and practical design considerations waspublished in1947[8].A simple reﬂector feed is achieved by placing a dipoleantenna in the focal point of a reﬂector and adding a reﬂecting plane sheet,half cylinder or hemisphere at an appropriate distance for constructive phasecontribution and illumination of the main reﬂector.The subtended half an-gle from the feed is normally≤70◦for proper illumination and reduced cross polarization.However,diﬀerences in E-and H-plane radiation from this typeof feed limits its applicability.In an early attempt of a self supported rear radiating feed a metallic diskwas placed in front of a circular waveguide going through the center of theparabolic reﬂector[8].The radiation patterns did deviate from expectationandﬁrst at a later stage it was found that the radiation from the feed is notspherical but toroidal with a phase center in the form of a ring laying be-tween the waveguide-and disk edge.The term ring focus feed was born andthe associated reﬂector shape should be that of a parabola rotated aroundthe focus ring i.e.being displaced by the ring focus radius.The radiation7Chapter2.Antenna Technologies for Satellite Earth Stations characteristics can be improved by introducing a ring under the disk or re-placing the disk by a cup.In the ring focus feed the T E11and T E12modes are excited and this combination causing almost straightﬁeld lines from the feed aperture plane with controlled illumination in the E-and H-planes as a result.The limiting factor is the impedance matching.2.2.2Dual Mode HornDual mode horns can be used for obtaining a uniform illumination of a re-ﬂector with steep edge taper[15].For a rectangular variant the T E10and T E30are excited by introducing a step causing a discontinuity.With proper amplitude and relative phase of these two modes the resulting aperture dis-tribution results in the desired conditions for uniform amplitude and phase. This step will also excite the T E20mode but if symmetry is maintained in the central plane this mode will not propagate.A serious limitation of the dual mode horn in many applications is its limited bandwidth.2.3Array AntennasArray antennas[16]are popular in specialized applications due to their low proﬁle and ability to scan the beam.Multiple antennas are grouped to yield highly directive patterns by adding theﬁeld constructively in the required directions and destructively elsewhere.Beam scanning is achieved by varying the phase excitation currents of the antenna array elements.Furthermore, the amplitude of the excitation currents can be varied to produce a wide range of radiation patterns with diﬀerent sidelobe characteristics.However, the technology is costly and the losses in the feed network is high.Also the presence of grating lobes during beam scanning is a restriction for satel-lite communications with stringent sidelobe requirements.However,with reduced component costs and advances in the array development this tech-nology is of interest not the least in airborne,train and automotive appli-cations.An example of a phased array antenna is the3D multi-role radar antenna,Figure2.2.2.4Earth Station Minimum Technical and Op-erational RequirementsEarth terminals in transmit mode(Tx)must comply with certain criteria not to interfere with neighboring satellites and these requirements are also recom-82.4Earth Station Minimum Technical and OperationalRequirementsFigure 2.2:Phased array antenna under test (The MFRA C-band navalradar).Image courtesy of Finmeccanica [23].mendations in receive mode (Rx).The sidelobe levels in the Tx-Ku-Satellite-band (13.75-14.50GHz)are required below certain sidelobe envelopes to be certiﬁed by the European Telecommunications Standards Institute,ETSI [24]29−25log 10θdBi for α<θ≤7◦,+8dBi for 7<θ≤9.2◦,32−25log 10θdBifor9.2<θ≤48◦,−10dBi for 48<θ◦.(2.1)For linear polarization the cross-polar sidelobe envelopes in the Tx-band as speciﬁed by the ETSI are19−25log 10θdBifor1.8<θ≤7◦,−2dBi for 7<θ≤9.2◦,(2.2)where θis the angle,in degrees,between the main beam axis and any direction towards the geostationary satellite orbit and within the bounds between 3◦North and 3◦South of the geostationary satellite orbit (as seen from the center of the earth).For antennas with a D/λratio ≤30,over the full extent of the antenna transmit frequency bands,the gain of the antenna sidelobe peaks should not exceed32−25log 10θdBifor α<θ≤48◦,−10dBifor 48<θ◦.(2.3)9Chapter2.Antenna Technologies for Satellite Earth Stations The angleαequals100λ/D or1◦whichever is greater.In case of non circular antenna apertures D is the dimension in the plane of the geosta-tionary orbit.Over the full extent of the antennas Tx-bands,no more than 10%of the antenna sidelobe peaks shall exceed the envelopes speciﬁed.Any individual peak shall not exceed those envelopes by more than6dB when θ>9.2◦and by more than3dB whenθ≤9.2◦.Over the full extent of the antenna Tx-bands,the antenna polarization discrimination in the direction of the satellite shall be≥35dB everywhere within a cone centered on the main beam axis,with the cone angle deﬁned by the pointing error or the -1dB contour of the main beam axis,whichever is greater.This is also the recommendation for the Rx-band.Earth stations may operate with a polar-ization discrimination down to25dB,provided that the power density of the transmitted carrier does not exceed34dBW/4kHz.The maximum allowed EIRP(Eﬀective Isotropic Radiated Power)is given for a G/T equal to0 dB/K(for a speciﬁc location,the satellite G/T given needs to be subtracted from the speciﬁed EIRP value).To protect from transmissions on neighbor-ing satellites,the antenna main beam axis shall not deviate by more than ±0.4◦from the nominal direction of the satellite along the geostationary or-bit,at all wind speeds at which the earth station may have to operate.The oﬀ-axis EIRP in any40kHz band in the direction of an adjacent satellite shall not exceed the following values31−25log10θdBW forα<θ≤7◦,+10dBW for7<θ≤9.2◦, 34−25log10θdBW for9.2<θ≤48◦,−8dBW for48<θ◦.(2.4)The orthogonally polarized component of the oﬀ-axis EIRP in any40kHz band should not exceed21−25log10θdBW for1.8<θ≤7◦,+0dBW for7<θ≤9.2◦.(2.5)In recent years many Ultra Small Aperture Terminals(USAT)have been developed especially for satcom on the move applications for trains,buses, ships&aircrafts etc where small antenna size is a requirement.The USAT size may have a D/λratio of≤30.As the original ETSI regulations evolved with large stationary earth stations in mind there have been a complementary standard for USAT namely the Standard M-x[25].This certiﬁcation can be given to USAT’s not fulﬁlling the ETSI requirements on co-and cross polarization but meets all other regulations.The certiﬁcation is initially102.4Earth Station Minimum Technical and Operational Requirementsgiven for a6month period in association with a valid transmission plan. The conditions are:•A minimum transmit cross-polar discrimination of20dB within the-1 dB contour of the main beam•A maximum allowed EIRP density in compliance with the oﬀ-axis emis-sions constraints from(2.4)•Antenna diameter≤2.4mThe co-and cross-polar sidelobe masks described are plotted in Figure 2.3.Figure2.3:Co-and cross-polar sidelobe envelopes including the20dB cross-polar discrimination requirement within a1dB contour of themain beam.Example antenna radiation patterns are included.11Chapter2.Antenna Technologies for Satellite Earth Stations 12Chapter3QuickWave-V2D&Genetic Algorithm for Simulation and Optimization3.1QuickWave-V2DWhen simulating the hat-fed reﬂector antenna;computational time and ac-curacy in the modeling are the two most important aspects when selecting an EM simulation software.As the hat-fed reﬂector antenna is axisymmetrical and a body of revolution(BOR)[26]it is possible to use a2D simulation tool and considerably reduce simulation time compared to3D modeling.QuickWave-V2D(QW-V2D)utilizes the conformal FDTD method in a vector two-dimensional(V2D)formulation,expressed in cylindrical coordi-nates[27].It incorporates models for curved boundaries,media interfaces, modal excitation,and parameter extraction.This V2D electromagnetic solver is applicable to the analysis of BOR-structures as large as300λ.The simulation time can be reduced by a factor100or more compared to brute force3D analysis.It was proven in[28]that structures maintaining axial symmetry of boundary conditions belong to a class of V2D problems.The total electromagneticﬁeld in such structures can be decomposed into a series of orthogonal modes,of diﬀerent angularﬁeld dependence of the cos(nφ)or sin(nφ)type,whereφis an angular variable of the cylindrical coordinate sys-tem and n=0,1,2..Each n-mode is analyzed separately in QW-V2D.Based on this the numerical analysis can be done in2D,over one half of the sym-metrical structure,with n predeﬁned as a parameter.The n-mode must not be confused with waveguide modes e.g.a QW-V2D analysis with n=1takes into account a composition of all circular waveguide modes T E1k and T M1m where k and m are arbitrary natural numbers.13Chapter3.QuickWave-V2D&Genetic Algorithm for Simulation and Optimization 3.2Optimization Methods Overview Optimization is a requirement in most systems and applications and it has found steady increased interest in electromagnetic problems in recent years.There are many optimization methods that can be applied e.g.:•Genetic Algorithm[29]•Particle swarm[30]•Diﬀerential evolution[30]•Hill climbing[31]•Quasi-Newtonian[31]•Simulated annealing[31]•Random walk[32]•Conjugate gradient[32]•Monte Carlo[32]The optimization methods can be grouped into the two main categories: Deterministic-and Stochastic optimization methods[32].Deterministic al-gorithms follow a rigorous procedure and its path and values of both design variables and functions are repeatable.Hill climbing is an example of a de-terministic algorithm and it will give identical output in any re-optimization. An inherent property of a stochastic optimization,on the other hand,is that it include randomness.The genetic algorithm is an example and the string or solution in the population will be diﬀerent for each optimization as the al-gorithm use pseudo random numbers and even if the end results may be very similar the path there is not exactly repeatable.There are also hybrid meth-ods e.g.Hill climbing with random restart.The method to chose depends on the type of problem to solve e.g.the number of variables and complexity. Work has also been done with focus on fast optimization of a special electro-magnetic problem[33,34].In this thesis we focus on the Genetic algorithm which is considered most suitable forﬁnding the global optimum of the rela-tively complex optimization problem of the hat feed.The genetic algorithm have been successfully applied not only in electromagnetics but also other ﬁelds of engineering,computer science andﬁnance[29].14。

Comet CAT-300天线调谐器说明书

QST April 2023 5Reviewed by Phil Salas, AD5X *************I suspect that one of the most com-mon accessories found in the ham shack is an antenna tuner. Andwhile autotuners have become quite popular, the manual antenna tuner fi lls the needs of many hams. The Comet CAT-300 antenna tuner is a rugged manual antenna tuner that handles power levels up to 300 W.Basic DescriptionLike most manual antenna tuners, the CAT-300 is a T -confi guration antenna tuner. This antenna tuner can handle up to 300 W PEP of RF from 160 through 6 meters. It includes a colorful 1.8 × 2.5-inch analog cross-needle meter that simultaneously displays for-ward, refl ected power, and SWR. There is a pair of high-voltage variable capacitors, and a tapped shunt inductor (actually, two series inductors). Controls in-clude a 30/300 W range selector, PEP and average power reading, a TUNER switch that bypasses the CAT-300 while leaving the power and SWR functions intact, an ANTENNA 1 or ANTENNA 2 switch, the normal transmit and antenna variable capacitor, and tapped inductor (BAND ) control. On the rear panel, you will fi nd three SO-239 connectors — one INPUT to connect your transceiver, and two outputs to connect your an-tennas (see Figure 2). Please note that there are two possibilities for the ANTENNA 2 output, using either the SO-239 or the WIRE ANT banana jack for a wire antenna. There is no internal balun. Figure 3 shows the internal view of the CAT-300, and the complete specifi cations are given in Table 2.The BAND switch selects the shunt inductor tap. This may or may not be associated with the listed band, depending on the mismatch. The CAT-300 two-sheet manual lists starting capacitor and inductor positions for a 50 Ω input and 50 Ω output. This was a good starting point for my adjustments, as I was gradually increasing the resistive mismatch. However, for real on-the-air SWR adjustments, I recommend the tech-nique described by Andrew S. Griffith, W4ULD, in “Getting the Most Out of Your T -Network AntennaComet CAT-300 1.8 – 50 MHz Manual Antenna TunerBottom LineFor those hams interested in a manualantenna tuner, the Comet CAT-300 is certainly worth considering. It should easily satisfy the needs of 100 – 200 W radios for most anyantenna system mismatches.Table 2Comet CAT-300Manufacturer’s Specifi cations (not tested by the ARRL Lab)Frequency range: 1.8 – 54 MHz Input impedance: 50 ΩOutput impedance: 10 – 600 ΩMaximum TX power: 300 W PEP Minimum SWR measurement power: 6 W Lighting power supply: 11 – 15 V dc at 250 mA maximum*Dimensions (width, height, depth): 9.8 × 3.9 × 9.5 inchesWeight: 6 pounds*The actual current was only about 20 mA. I suspect that the original CAT -300 used an incandescent lamp for meter illumination. When this was changed to LEDs, apparently the current spec was not revised.Figure 2 — The Comet CAT-300 rear panel.6 April 2023 QST Tuner” in the January 1995 issue of QST . This entails the following procedure:1. Start with both capacitors in their center (half-meshed) posi-tions.2. Switch the shunt inductor to fi nd maximum receiver noise.3. Transmit 5 – 10 W and rotate the output capacitor, looking for an SWR dip.4. If no dip is seen, switch the inductor up or down and try again.5. Once an SWR dip is found, adjust the input capacitor for best SWR.6. Rock the output capacitor, and vary the input capacitor, until you fi nd the lowest SWR.My matching tests are shown inTable 3. I found that the adjustments were very touchy on 20 meters and above. However, it was fairly easy to null the SWR using the analog meter on the CAT-300. The input SWR was measured using a NIST-traceable power meter, as I wanted to more precisely measure the matched SWR.For these resistive SWR tests, all best SWR adjust-ments coincided with the corresponding band setting, except the high impedance 10-meter tests. In these cases, I had to use the 6-meter inductor position. And I could not fi nd a tuning solution better than 2:1 SWR for the 6.25 Ω (8:1 SWR) low-impedance test on 10 meters. Also, as you can see in Figure 3, there are insulated shaft extensions on the two variable capaci-tors. Other manual antenna tuners I’ve reviewed just used the plastic knobs to isolate the user from the high RF voltages on the capacitors, but I would often get RF burns from the setscrews in the knobs. This is not a problem with the CAT-300.Table 3Comet CAT-300 Resistive Load and Loss TestingVSWR/Impedance160 M80 M40 M20 M10 M6 M10:1/5 Ω Loss (%) 65% 46% 40% 45% 19% 23%VSWR 1.1:1 1.1:1 1.1:1 1.1:1 1.2:1 1.2:18:1/6.25 Ω Loss (%) 58% 41% 30% 26% 10% 15%VSWR 1:1 1.1:1 1.2:1 1.2:1 2:1 1.3:14:1/12.5 Ω Loss (%) 44% 29% 20% 24% <5% 6%VSWR 1.1:1 1.1:1 1.2:1 1.1:1 1.2:1 1.1:13:1/16.7 Ω Loss (%) 37% 23% 20% 19% <5% 13%VSWR 1.1:1 1.1:1 1.1:1 1.1:1 1.1:1 <5%2:1/25 Ω Loss (%) 26% 20% 16% 18% 6% 14%VSWR 1.2:1 1.1:1 1:1 1.1:1 1:1 1.1:11:1/50 Ω Bypass Loss 0% 0% 0% 1% 2% 3%Bypass VSWR 1:1 1:1 1:1 1:1 1.1:1 1.3:12:1/100 Ω Loss (%) 18% 10% 10% 16% 10% 7%VSWR 1.1:1 1:1 1:1 1.1:1 1.3:1 1.1:13:1/150 Ω Loss (%) 16% 10% 7% 16% 10% <5%VSWR 1.1:1 1.1:1 1.1:1 1.1:1 1.1:1 1.1:14:1/200 Ω Loss (%) 12% 8% 8% 20% 12% <5%VSWR 1:1 1:1 1.1:1 1.2:1 1.1:1 1.1:18:1/400 Ω Loss (%) 12% 12% 15% 23% 26% 40%VSWR 1:1 1.1:1 1.2:1 1.1:1 1.3:1 1.1:110:1/500 Ω Loss (%) 15% 12% <5% 25% 30% 44%VSWR 1.1:1 1.1:1 1.1:1 1.1:1 1.2:1 1.6:1Table 4Comet CAT-300 SWR and Power Reading AccuracyLow ImpedanceHigh Impedance30 W Scale300 W ScaleBand 2:1 SWR 3:1 SWR 2:1 SWR 3:1 SWR 10 W 20 W 50 W 80 W 160 M 1.4:1 1.9:1 1.7:1 2.7:1 9.5 W 20 W 50 W 80 W 20 M 1.4:1 2.2:1 1.5:1 2.4:1 8.7 W 16 W 50 W 70 W 10 M 1.4:1 2.0:1 1.6:1 2.5:1 8.2 W 15 W 50 W 70 W 6 M1.3:11.8:11.7:12.5:19 W17 W50 W75 WFigure 3 — The Comet CAT-300 internal view.Next, I measured the SWR and power readings versus my NIST-traceable equipment with the CAT-300 placed in the bypass mode. The CAT-300 readings are my best attempts to interpolate the readings on the analog CAT-300 meter. The results are shown in Table 4.The SWR readings are reasonably accurate when the impedance is high. The low-impedance SWR mea-surements are much less accurate. However, the SWR meter is quite adequate for dipping the SWR during tuning.Finally, I looked at the peak meter-reading position.T he peak reading meter circuitry is not powered. Ap- parently, a larger capacitor is used to hold the sampled energy a little longer than normal. However, this also means it takes longer to charge this capacitor and, thus, display the peak power. On CW, I found that it took four dits before a true peak reading could be ob-served. This was more difficult on SSB. I found that I needed to talk fast and continuously for several sec-onds in order to see a peak reading. However, the CAT-300 meter only ever showed about 80% of the peak reading displayed on my Array Solutions Power-Master.ConclusionThe Comet CAT-300 manual antenna tuner is a well-made and rugged product. I was particularly impres-sed with the bypass SWR, especially on 10 and6 meters. This shows that Comet was careful to ensure that stray wiring inductances were kept to a minimum. I was also pleased with the insulated vari-able capacitor shafts.Manufacturer: Comet Co., LTD (Japan). Distributed in North America by the NatCommGroup, NCG Compa-nies Inc., 15036 Sierra Bonita Lane, Chino, CA 91710. . Price: $280. QST April 2023 7。

ETS-Lindgren EMCO Model 3142C BiConiLog 产品介绍说明书

ETS-Lindgren’s EMCO Model 3142C BiConiLog AntennaFeatures:●26 MHz - 3 GHz Frequency Range ●Emissions Testing:-- ANSI C63.4-- FCC-15 and FCC-18-- EN 55022●Individually Calibrated:--1m per SAE ARP 958--3m and 10m per ANSI C63.5●Avg. 2:1 VSWR Above 80 MHz ●Fits Compact Chambers ●Tough Powder Coat Finish ●Two Year WarrantyTMETS-Lindgren’s EMCO Model 3142C BiConiLog is a hybrid antenna that combines innovative design, compact size, and excellent performance. This antenna enables users to measure a frequency range of 26 MHz to 3.0 GHz in one sweep, negating the need for multiple antennas and time-consuming equipment setup. This single sweep capability removes the need for multiple antennas and additional equipment,which improves accuracy and saves time and money.This BiConiLog is designed as a dual-purpose antenna that can be used for both immunity and emission testing.From 26 MHz to 60 MHz, the Model 3142C antenna with optional end plates exhibits an average 5.5 dB gain improvement vs. typical hybridantennas. At some frequencies, a 10 dB gain improvement is achieved.This model replaces the EMCO Model 3142 and 3142B, and when used with optional end plates, is identical to the former Model 3141. The optional end plates are available to improve gain for immunity testing. These plates can easily be attached and detached by hand using screw knobs. Individual antenna calibration data- without the end plates attached- is provided for emission testing.Standard Configuration●Antenna●Individually c alibrated:-- 1m per SAE ARP 958-- 3m and 10 m per ANSI C63.5●Actual a ntenna f actors a nd a s igned Certificate o f C alibration C onformance included i n m anual ●ManualBiConiLog EMC AntennasModel 3142COptions●Optional T B ow-Tie e nd p lates (shown b elow)●ETS-Lindgren o ffers s everal n on-metallic,non-reflective t ripods f or u se a t E MC t est sites. F or e asy h orizontal a nd v erticalpolarization c hanges, t he M odel 7-TR t ripod is r ecommendedETS-Lindgren’s EMCO Model 3142C BiConiLogAntenna with Optional End Plates1981Model 3142C Antenna Factor (without End Plates)Model 3142C Forward Power 1m with End PlatesModel 3142C Forward Power 3m with End Plates Model 3142C Gain with End PlatesElectrical SpecificationsMODEL FREQUENCY VSWR MAXIMUM IMPEDANCE CONNECTORSRANGE RATIO CONTINUOUS(NOMINAL)(AVG)POWER3142C26 MHz – 60 MHz2:1500 W50ΩType N female (1)60 MHz – 600 MHz2:1 1 kW50ΩType N female (1)600 MHz – 1 GHz2:1500 W50ΩType N female (1)1 GHz – 3 GHz2:1200 W50ΩType N female (1)Physical SpecificationsMODEL WIDTH DEPTH HEIGHT WEIGHT 3142C135.0cm124.5cm75.0 cm 4.0 kg without optional end plates53.1in49.0 in29.5in8.8 lb3142C137.4cm132.1cm76.2 cm 6.7 kg with optional end plates54.1in52.0 in30.0in14.7 lb。

ANTENNA TUNING UNIT

专利名称：ANTENNA TUNING UNIT发明人：HAMILTON, George, Timothy,SANDS, Donald, James,COWLES, Russell, Wayne 申请号：US2014/070001申请日：20141212公开号：WO2015/094962A1公开日：20150625专利内容由知识产权出版社提供专利附图：摘要：A system, apparatus, and method directed to impedance matching an antenna with a transmitter for non-directional radio beacons. The apparatus includes an L-type impedance network comprising non-capacitive elements and at least one variableinductor on each branch of the impedance network. Also, system, apparatus, and method directed to providing a low power signal for tuning the antenna. The apparatus includes an impedance matching network and a signal generator. Also, a system, apparatus, and method directed to providing an estimate of near-field strength of a signal from an antenna. The apparatus includes an impedance matching network, a near-field signal strength detector, and microcontroller configured to estimate the near-field signal strength. Corresponding systems includes using the respective apparatuses between an antenna and a transmitter. Corresponding methods are directed to the use of the apparatuses and systems.申请人：SOUTHERN AVIONICS CO.地址：5055 Belmont Street Beaumont, TX 77707 US国籍：US代理人：FLADUNG, Richard, D.更多信息请下载全文后查看。

Audix Performance Series 演讲系列说明书

AUDIX PERFORMANCE SERIES SCAN. SYNC. PLAY!503.682.6933©2016 Audix Corporation All RightsReserved.Audix and the Audix Logo aretrademarks of Audix Corporation.January 2016 PreliminaryWhether you are a vocalist, musician, performer or presenter, the Audix Performance Series is designed to take the mystery out of wireless with a professional-grade system that is simple, reliable and versatile.Going from set up to performance is as easy as:SCANSYNCPLAY!RECEIVERSAvailable in single and dual rack mountable models, the receivers for the Audix Performance Series feature a contemporary design, rugged construction and intuitive menus .Single Channel R41 R61Dual Channel (R42 and R62) | Dual channel systemhoused within a durable rack mount receiver. Operates with one set of antennas and one power supply.. 32 MHz Extended spectrum receiver . Microprocessor-controlledantenna diversity. 8 compatible system operation . 106 pre-coordinated frequencies for quick, easy and reliable set up . 300’ (91 Meters) operating range . Metal rack mountable chassis . RF and AF indicators. High contrast LCD display. One-touch auto scan searches for clear channel . One-touch sync links transmitter to receiver via infrared beam. Choice of balanced XLR or ¼” outputs. Soft keys control output levels, squelch, pilot, lockout . Wide selection of handheld, instrument, headset and lavalier options. 64 MHz Wide spectrum tuning receiver. True diversity, dual receiver modules . 16 compatible system operation . 207 pre-coordinated frequenciesfor quick, easy and reliable set up . 2560 tunable frequencies. 300’ (91 Meters) operating range . Metal rack mountable chassis . RF and AF indicators. High contrast LCD display. One-touch auto scan searches for clear channel . One-touch sync links transmitter to receiver via infrared beam. Choice of balanced XLR or ¼” outputs. Soft keys control output levels, squelch, pilot, lockout . Wide selection of handheld, instrument, headset and lavalier optionsFour dual systems may be used with one ADS48 antenna distribution system.R41R61TRANSMITTERSAudix Performance Series transmitters consist of both handheld and bodypack designs.Handheld H60 | The H60 features an elegantlydesigned slim line body that is compact, well-balanced and comfortable to hold.SYSTEMSBelow are some of the system options available. Systems include receiver, antennas, power supply, bodypack or handheld transmitter and microphone.. 64 MHz Wide spectrum transmitter(works with all Performance Series receivers). Durable metal housing. May be used with dynamic (OM Series) andcondenser microphones (VX5). AF and RF gain control. Modular and interchangeable capsule assemblies . High contrast LCD display with group, channeland battery indicator. Soft mute switch. 10 Hour Run Time - AA batteries. 64 MHz Wide spectrum transmitter(works with all Performance Series receivers). Precision metal housing . Lightweight, slim design . Modular antenna design. May be used with lavalier, head worn andinstrument mics as well as electric guitar and bass. AF and RF gain control. High contrast LCD display with group, channeland battery indicator . Soft mute switch. 10 Hour Run Time - AA batteriesBodypack B60 | The Audix Performance Seriesbody pack system is very contemporary in design, rugged,comfortable to wear and easy to use.1.HANDHELDOM2 | OM5 | VX54. INSTRUMENTGuitar | Sax | Flute5. COMBOGuitar and Vocal | Lavalier and Vocal2. LAVALIERL5 | ADX103. HEADWORNHT2 | HT5 | HT7SPECIFICATIONSH60B60RF Power Output 10 mW, 40 mW 10 mW, 40 mW Frequency Bandwidth 64 MHz64 MHzGain Controls 0 dB, -6 dB, -12 dB 0 db, -6 dB, -12 dB Input Connector n/a 3 pin mini-XLR Battery (not included) 2 AA 1.5 V 2 AA 1.5 V Current Consumption 110 mA typical110 mA typicalBattery Life Approximately 10 hours(depending on battery type and usage)Approximately 10 hours(depending on battery type and usage)Input Impedance n/aMic: 10k Ohm, Line: 1M OhmMax Sound Pressure Level >140 dB (depending on capsule)approx. 128 db to140 dB (depending on mic)Dimensions 2.1” diameter body, 10.43” (L), 53 mm diameter body, 265 mm (L)67 mm (W) x 90 mm (L) x 17 mm (D)2.6" (W) x 3.5" (L) x .67" (D)Net Weight11.0 oz / 312 g (without battery)3.0 oz / 85 g (without battery)Specifications subject to change without notice.R41R61Frequency Range 522 MHz – 554 MHz / 554 MHz - 586 MHz 522 MHz – 586 MHz Bandwidth 32 MHz64 MHzCompatible Systems 8 compatible system operation 16 compatible system operation Switchable Frequencies 106 preset frequencies 207 preset frequenciesManual Mode n/a2560 frequencies (spaced 25 KHz apart)Frequency Response 45 Hz – 18 kHz 45 Hz – 18 kHz Signal to Noise Ratio >105 dB >105 dB Compander System 2:12:1Pilot Tone 32 kHz32 kHzReceiving System Single tuner, antenna diversityDual tuner, true diversitySignal-to-Noise Ratio 105 dB at 30 kHz deviation (IEC-weighted)112 dB at 30 kHz deviation (IEC-weighted)Total Harmonic Distortion ≤.7% (10 kHz deviation at 1 kHz)≤.4% (10 kHz deviation at 1 kHz)Sensitivity5 dBμV (S/N 60 dB at 25 kHz deviation, IEC-weighted) 5 dBμV (S/N 60 dB at 25 kHz deviation, IEC-weighted) Intermediate Frequency 110.6 MHz, 10.7 MHz110.6 MHz, 10.7 MHzAudio Output (AF=0)1/4" 1100 mV (at 1 kHz,)10 kHz deviation, 10 k ohm load Balanced: 2200 mV (at 1 kHz,) 10 kHz deviation, 600 ohm load 1/4" 1100 mV (at 1 kHz,)10kHz deviation, 10k ohm load Balanced: 2200mV (at 1 kHz,) 10kHz deviation, 600 ohm load Output Connectors 1/4", XLR1/4", XLRNominal / Peak Deviation Balanced: -12 to +9 dBuLine: -24 to +4 dBu (adjustable in 3 dB-steps)Balanced: -12 to +9dBuLine: -24 to +4dBu (adjustable in 6 dB-steps)Adjacent Channel Rejection >65 dB >65 dB Intermodulation Spacing >65 dB >65 dB Image Rejection >70 dB >70 dB Range 300', (91 M)300', (91 M)Power Supply 100 - 240V / 50 - 60 Hz, 12V DC, 1A100 - 240V / 50 - 60 Hz, 12V DC, 1ADimensions 205 mm (W) x 206 mm (D) x 44 mm (H)406 mm (W) x 209 mm (D) x 44 mm (H) (R42)205 mm (W) x 206 mm (D) x 44 mm (H)406 mm (W) x 209 mm (D) x 44 mm (H) (R62)Net Weight1.92 lbs. / 870 g4.75 lbs. / 2.1 kg (R42)2.43 lbs. / 1.1 kg4.75 lbs. / 2.1 kg (R62)。

L3Harris Command and Control Mobile TOC说明书

KEY BENEFITS>Preconfigured for near plug- and-play deployment with the L3Harris AN/PRC-158 >Dual-channel LOS, wideband, legacy and MUOS SATCOM connectivity >Touchscreen PC supports all Windows-based C2 programs >Can be integrated with the L3Harris RF-7800I Tactical Networking Intercom SystemRAPIDLY DEPLOYED,USER-FRIENDLY NETWORK SOLUTIONIdeal for nomadic missions, this wheeled, all-in-one system includes wideband/multiband and power amplifiers, AC and DC-DC power, SATCOM, LOS, wideband and narrowband ports, an Ethernet® switch and a dual audio channel loud speaker. All mounting and cabling are pre-configured allowing users to connect only power and antennas for immediate operation.Equipped with a PC and monitor, the L3Harris Command and Control Mobile TOC provides fast access to C2 programs with flexible support for any Windows®-based software. The ruggedized PC features touchscreen technology and a sunlight-readable display.L3HARRIS COMMAND AND CONTROL MOBILE TOCThe L3Harris Command and Control Mobile TOC requires minimal setup, connections or configuration to establish a fully functional Tactical Operations Center. Designed for use with the L3Harris AN/PRC-158 Multi-channel Manpack, this C2 solution allows users to quickly establish dual-channel Line-Of-Sight (LOS), SATCOM and wideband network connectivity.Non-Export Controlled InformationL3Harris Technologies is an agile global aerospace and defense technology innovator, delivering end-to-end solutions that meet customers’ mission-critical needs. The company provides advanced defense and commercial technologies across air, land, sea, space and cyber domains.L3Harris Command and Control Mobile TOC © 2019 L3Harris Technologies, Inc. | 09/2019 DS667GENERALRT Nomenclature12206-0100-01 (TIB)RT 2034A P C U (SAASM GPS) RT 2034 P C U (commercial GPS)Frequency Range 30 MHz-2.5 GHzNarrowband: VHF: 30-225 MHz, UHF: 225-520 MHz, 762-874 MHzSATCOM: RX: 243-270 MHz, TX: 292-318 MHz Wideband: UHF: 225-520 MHz L-BAND: 762 MHz-2.5 GHzChannel Spacing/Bandwidth Narrowband: 8.33 kHz, 12.5 kHz, 25 kHz Wideband: 1.2 MHz, 5 MHzFM Deviation: 5 kHz, 6.5 kHz, 8 kHz Net Presets 99 system presets per channelGPSSAASM receiver (commercial GPS optional)Management Tool Communications Planning Application (CPA); JENM compatibleFrequency Tuning 10 Hz from 30-520 MHz100 Hz from 762 MHz-2.5 GHz Software EnvironmentSCA v2.2.2TRANSMITTERPower OutputCH1:VHF Low (30-90 MHz): 50 watts PEPVHF High/UHF (90-450 MHz): 50 watts PEP UHF (450-512 MHz): Greater than 20 watt PEP Wideband (225-450 MHz): 50 watts PEP and AverageWideband (450 MHz-2 GHz): 20 watts PEP CH2:Narrowband: 10 WWideband: 20 W peak/10 W average (max)Harmonic Suppression > 53 dBc Spurious Suppression> 53 dBcRECEIVERSensitivityLOS FM 30-512 MHz: -116 dBm LOS AM 90-512: -103.5 dBm with 30% modulation Adjacent Channel Rejection > -40 dBSquelchDigital (CDCSS or CTCSS), tone, noise or nonePOWERPower Input24-32 VDC or 93-265 VACSECURITYEncryption Sierra™ II based Type 1 (Suite A/B) NSA Certified TOP SECRET and below Encryption ModesKY-57 (VINSON), KYV-5 (ANDVT), KG-84C, FASCINATOR, HAIPE (PPK, FFV), AES (Type 1 & 3)MODES AND WAVEFORMSNarrowband Waveforms AM/FM, VHF/UHF LOS, SINCGARS, HAVEQUICK I/II, HPW (SATURN, APCO P25 capable)Wideband WaveformsSRW, ANW2®C (WNW capable)UHF SATCOM WaveformsMIL-STD-188-181B dedicated channels MIL-STD-188-182A, 183A DAMAMIL-STD-188-181C, 183B IW Phase 1 HPW MUOSVoice and Data ModesSimplex or half duplexMIL-STD-188-113 CVSD STANAG 4198 LPC-10e STANAG 4591 MELPe Full duplex capablePHYSICALDimensions (H x W x D)12.5 x 25 x 23 in (31.75 x 63.5 x 58.4 cm)Weight 93 lbs w/o R/T Color/FinishTanINTERFACESDataEthernet, RS-232, EIA-422, PPP, USB Audio VIC-1, VIC-3, LS-671 compatible VideoHDMI OutputAntenna PortCH1:VHF Low: 50 Ohm BNCVHF High/UHF: 50 Ohm BNC UHF SATCOM: 50 Ohm BNC Wideband: 50 Ohm N-Type CH2:Wideband: 50 Ohm N-Type Function Knob OFF, ON, LD, ZRemote ControlRF-7800I Compatible, USB, RS-232, Remote Keypad Display Unit (RKDU), Software Keypad Display UnitSTANDARD KIT INCLUDES12206-0300-01Multi-channel Manpack Case 12206-0500-01Accessory KitOPTIONAL ACCESSORIESRF-3193TB-ATXXXTACT MAST ANT SET, 30-88,108-512, 550-2000 MHZRF-3082-AT001Antenna, Foldable, UHF SATCOM, MUOS ATP RF-340M-DK001Kit, Dismount AntennasPlease visit for more information.1025 W. NASA Boulevard Melbourne, FL 32919。

微带耦合器的中英文对照翻译

Design and Analysis of Wideband Nonuniform Branch Line Coupler and Its Application in a Wideband Butler MatrixYuli K. Ningsih,1,2 M. Asvial,1 and E. T. RahardjoAntenna Propagation and Microwave Research Group (AMRG), Department of Electrical Engineering, Universitas Indonesia, New Campus UI, West Java, Depok 16424, Indonesia Department of Electrical Engineering, Trisakti University, Kyai Tapa, Grogol, West Jakarta 11440, IndonesiaReceived 10 August 2011; Accepted 2 December 2011Academic Editor: Tayeb A. DenwdnyCopyright © 2012 Yuli K. Ningsih et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.AbstractThis paper presents a novel wideband nonuniform branch line coupler. An exponential impedance taper is inserted, at the series arms of the branch line coupler, to enhance the bandwidth. The behavior of the nonuniform coupler was mathematically analyzed, and its design of scattering matrix was derived. For a return loss better than 10 dB, it achieved 61.1% bandwidth centered at 9GHz. Measured coupling magnitudes and phase exhibit good dispersive characteristic. For the 1dB magnitude difference and phase error within 3∘, it achieved 22.2% bandwidth centered at 9GHz. Furthermore, the novel branch line coupler was implemented for a wideband crossover. Crossover was constructed by cascading two wideband nonuniform branch line couplers. These components were employed to design a wideband Butler Matrix working at 9.4GHz. The measurement results show that the reflection coefficient between the output ports is better than 18dB across 8.0GHz–9.6GHz, and the overall phase error is less than 7.1. IntroductionRecently, a switched-beam antenna system has been widely used in numerous applications, such as in mobile communication system, satellite system, and modern multifunction radar. This is due to the ability of the switched-beam antenna to decrease the interference and to improve the quality of transmission and also to increase gain and diversity.The switched-beam system consists of a multibeam switching network and antenna array. The principle of a switched-beam is based on feeding a signal into an array of antenna with equal power and phase difference. Different structures of multibeam switching networks have been proposed, such as the Blass Matrix, the Nolen Matrix, the Rotman Lens, and the Butler Matrix .One of the most widely known multibeam switching networks with a linear antenna is the Butler Matrix. Indeed, it seems to be the most attractive option due to its design simplicity and low power loss .In general, the Butler Matrix is an N × N passive feeding network, composed of branch line coupler, crossover, and phase shifter. The bandwidth of the Butler Matrix is greatly dependent on the performance of the components. However, the Butler Matrix has a narrow bandwidth characteristic due to branch line coupler and crossover has a limited bandwidth.As there is an increased demand to provide high data throughput , it is essential that the Butler Matrix has to operate over a wide frequency band when used for angle diversity. Therefore, many papers have reported for the bandwidth enhancement of branch line coupler . In reference , design and realization of branch line coupler on multilayer microstrip structure was reported. These designs can achieve a wideband characteristic. However, the disadvantages of these designs are large in dimension and bulk.Reference introduces a compact coupler in an N-section tandem-connected structure. The design resulted in a wide bandwidth. Another design, two elliptically shaped microstrip lines which are broadside coupled through an elliptically shaped slot, was employed in . This design was used in a UWB coupler with high return loss and isolation. However, these designs require a more complex manufacturing.In this paper, nonuniform branch line coupler using exponential impedance taper is proposed which can enhance bandwidth and can be implemented for Butler Matrix, as shown in Figure 1. Moreover, it is a simple design without needs of using multilayer technology. This will lead in cost reduction and in design simplification.Figure 1:Geometry structure of a new nonuniform branch line coupler design with exponential impedance taper at the series arm.To design the new branch line coupler, firstly, the series arm’s impedance is modified. The shunt arm remains unchanged. Reduced of the width of the transmission line at this arm is desired by modifying the series arm. Next, by exponential impedance taper at the series arm, a good match over a high frequency can be achieved.2. Mathematical Analysis of Nonuniform Branch Line CouplerThe proposed nonuniform branch line coupler use λ/4 branches with impedance of 50Ω at the shunt arms and use the exponential impedance taper at the series arms, as shown in Figure 1. Since branch line coupler has a symmetric structure, the even-odd mode theory can be employed to analyze the nonuniform characteristics. The four ports can be simplified to a two-port problem in which the even and odd mode signals are fed to two collinear inputs [22]. Figure 2 shows the schematic of circuit the nonuniform branch line coupiers.Figure 2:Circuit of the nonuniform branch line coupler.The circuit of Figure 2 can be decomposed into the superposition of an even-mode excitation and an odd-mode excitation is shown in Figures and .Figure 3:Decomposition of the nonuniform branch line coupler into even and odd modes of excitation.The ABCD matrices of each mode can be expressed following . In the case of nonuniform branch line coupler, the matrices for the even and odd modes become:A branch line coupler has been designed based on the theory of small reflection, by the continuously tapered line with exponential tapers , as indicated in Figure 1, wherewhich determines the constant as:Useful conversions for two-port network parameters for the even and odd modes of S11and S21 can be defined as follows :whereSince the amplitude of the incident waves for these two ports are ±1/2, the amplitudes of the emerging wave at each port of the nonuniform branch line coupler can be expressed asParameters even and odd modes of S11 nonuniform branch line coupler can be expressed as and as follows:An ideal branch line coupler is designed to have zero reflection power and splits the input power in port 1 (P1) into equal powers in port 3 (P3) and port 4 (P4). Considering to , anumber of properties of the ideal branch line coupler maybe deduced from the symmetry and unitary properties of its scattering matrix. If the series and shunt arm are one-quarter wavelength, by using , resulted in S11 = 0.As both the even and odd modes of S11 are 0, the values of S11 and S21 are also 0. The magnitude of the signal at the coupled port is then the same as that of the input port.Calculating and under the same , the even and odd modes of S21 nonuniform branch line coupler will be expressed as follows inBased on ,S11 can be expressed as follows Following ,S41 nonuniform branch line coupler can be calculating as followsFrom this result, both S31 and S41 nonuniform branch line couplers have equal magnitudes of −3dB. Therefore, due to symmetry property, we also have thatS11=S22=S33=S44=0,S13=S31，S14=S41，S21=S34, and . Therefore, the nonuniform branch line coupler has the following scattering matrix in3. Fabrication and Measurement Result of Wideband Nonuniform Branch Line CouplerTo verify the equation, the nonuniform branch line coupler was implemented and its -parameter was measured. It was integrated on TLY substrate, which has a thickness of 1.57mm. Figure 4shows a photograph of a wideband nonuniform branch line coupler. Each branch at the series arm comprises an exponentially tapered microstrip line which transforms the impedance from ohms to ohms. This impedance transformation has been designed across a discrete step length mm.Figure 4:Photograph of a proposed nonuniform branch line coupler.Figure 5 shows the measured result frequency response of the novel nonuniform branch line coupler. For a return loss and isolation better than 10dB, it has a bandwidth of about 61.1%; it extends from 7 to 12.5GHz. In this bandwidth, the coupling ratio varies between 2.6 dB up to 5.1dB. If the coupling ratio is supposed approximately 3 ±1dB, the bandwidth of about 22.2% centered at 9GHz.Figure 5:Measurement result for nonuniform branch line coupler.As expected, the phase difference between port 3 (P3) and port 4 (P4) is 90°. At 9 GHz, thephases of and are 85.54° and 171°, respectively. These values differ from ideal value by 4.54°. The average phase error or phase unbalance between two branch line coupler outputs is about 3°. But even the phase varies with frequency; the phase difference is almost constant and very close to ideal value of 90° as shown in Figure 6.Figure 6:Phase characteristic of nonuniform branch line coupler.4. Design and Fabrication of the Wideband Butler MatrixFigure 7 shows the basic schematic of the Butler Matrix . Crossover also known as 0dB couplers is a four-port device and must provide for a very good matching and isolation, while the transmitted signal should not be affected. In order to achieve wideband characteristic crossover, this paper proposes the cascade of two nonuniform branch line couplers.Figure 7:Basic schematic of the Butler Matrix .Figure 8shows the microstrip layout of the optimized crossover. The crossover has a frequency bandwidth of 1.3GHz with VSWR = 2, which is about 22.2% of its centre frequency at 9 GHz. Thus, it is clear from these results that a nonuniform crossover fulfills most of the required specifications, as shown in Figure 9.Figure 8:Photograph of microstrip nonuniform crossover.Figure 9:Measurement result for nonuniform crossover.Figure 10 shows the layout of the proposed wideband Butler Matrix. This matrix uses wideband nonuniform branch line coupler, wideband nonuniform crossover, and phase-shift transmission lines.Figure 10:Final layout of the proposed wideband Butler Matrix .The wideband Butler Matrix was measured using Network Analyzer. Figure 11 shows the simulation and measurement results of insertion loss when a signal was fed into port 1, port 2, port 3, and port 4, respectively. The insertion loss are varies between 5dB up to 10dB. For the ideal Butler matrix, it should be better than 6dB. Imperfection of fabrication could contribute to reduction of the insertion loss.Figure 11:Insertion loss of the proposed Butler Matrix when different ports are fed.The simulated and measured results of the return loss at each port of the widedend Butler Matrix is shown in Figure 12. For a return loss better than 10dB, it has a bandwidth about17% centered at 9.4GHz.Figure 12:Return loss of the proposed Butler Matrix when different ports are fed.Figure 13 shows the phase difference of measured results when a signal was fed into port 1, port 2, port 3, and port 4, respectively. The overall phase error was less than 7°. There are several possible reasons for this phase error. A lot of bends in high frequency can produce phase error. Moreover, the imperfection of soldering, etching, alignment, and fastening also could contribute to deviation of the phase error.Figure 13:Phase difference of the proposed Butler Matrix when different ports are fed.Table 1shows that each input port was resulted a specific linear phase at the output ports. The phase differences each between the output ports are of the same value. The phase difference can generate a different beam ( θ). If port 1 (P1) is excited, the phase difference was 45°, the direction of generated beam ( θ) will be 14.4°for 1L. It is summarized in Table 1.Table 1:Output phase difference and estimated direction of generated beam.5. ConclusionA novel nonuniform branch line coupler has been employed to achieve a wideband characteristic by exponential impedance taper technique. It is a simple design without needs of using multilayer technology and this will lead to cost reduction and design simplification. The scattering matrix of the nonuniform branch line coupler was derived and it was proved that the nonuniform branch line coupler has equal magnitude of −3dB. Moreover, the novel nonuniform branch line coupler has been employed to achieve a wideband 0dB crossover. Furthermore, these components have been implemented in the Butler Matrix and that achieves wideband characteristics.ReferencesT. A. Denidni and T. E. Libar, “Wide band four-port butler matrix for switched multibeam antenna arrays,” in Proceedings of the IEEE International Symposium on Personal, Indoor and Mobile Radio Communications (PIMRC '03), vol. 3, pp. 2461–2464, 2003. View at Publisher ·View at Google Scholar2 E. Siachalou, E. Vafiadis, S. S. Goudos, T. Samaras, C. S. Koukourlis, and S. Panas, “On the design of switched-beam wideband base stations,” IEEE Antennas and Propagation Magazine, vol. 46, no. 1, pp. 158–167, 2004. View at Publisher ·View at Google Scholar ·View at Scopus3P. S. Hall and S. J. Vetterlein, “Review of radio frequency beamforming techniques for scanned and multiple beam antennas,”IEE Proceedings H, vol. 137, no. 5, pp. 293–303, 1990. View at Scopus4W-D. Wirth, Radar Techniques Using Array Anney, IEE Publishers, Stevenage, UK, 2001.5S. Y. Zheng, S. H. Yeung, W. S. Chan, and K. F. Man, “Broadband butler matrix optimized using jumping genes evolutionary algorithm,” in Proceedings of the IEEE International Conference on Industrial Technology (IEEE ICIT '08), Hong Kong, April 2008. View at Publisher ·View at Google Scholar6K. Wincza and K. Sachse, “Broadband Butler matrix in microstrip multilayer technology designed with the use of three-section directional couplers and phase correction Networks,” in Proceedings of the 18th International Conference on Microwave Radar and Wireless Communications(MIKON '10), Cracow, Poland, June 2010.7 A. M. El Tager and M. A. Eleiwa, “Design and implementation of a smart antenna using butler matrix for ISM band,”in Proceedings of the Progress in Electromagnetics Research Symposium (PIERS '09), pp. 571–575, Beijing, China, March 2009.8Y. S. Jeong and T. W. Kim, “Design and analysis of swapped port coupler and its application in a miniaturized butler matrix,”IEEE Transactions on Microwave Theory and Techniques, vol. 58, no. 4, pp. 764–770, 2010. View at Publisher ·View at Google Scholar ·View at Scopus9 C. Collado, A. Grau, and F. De Flaviis, “Dual-band butler matrix for WLAN systems,”in IEEE MTT-S International Microwave Symposium Digest, vol. 2005, pp. 2247–2250, 2009. View at Publisher ·View at Google Scholar10K. Wincza, S. Gruszczynski, and K. Sachse, “Integrated four-beam dual-band antenna array fed by broadband Butler matrix,” Electronics Letters, vol. 43, no. 1, pp. 7–8, 2007. View at Publisher ·View at Google Scholar ·View at Scopus11T. N. Kaifas and J. N. Sahalos, “On the design of a single-layer wideband Butler matrix for switched-beam UMTS system applications,” IEEE Antennas and Propagation Magazine, vol. 48, no. 6, pp. 193–204, 2006. View at Publisher ·View at Google Scholar ·View at Scopus12K. Wincza and S. Gruszczynski, “A broadband 4 × 4 butler matrix for modern-day antennas,” in Proceedings of the 35th European Microwave Conference, pp. 1331–1334, Paris, France, October 2005. View at Publisher ·View at Google Scholar13S. Gruszczyński, K. Wincza, and K. Sachse, “Reduced sidelobe four-beam N-element antenna arrays fed by 4 × 4 N butler matrices,” IEEE Antennas and Wireless PropagationLetters, vol. 5, no. 1, pp. 430–434, 2006. View at Publisher ·View at Google Scholar ·View at Scopus14Y. C. Su, M. E. Bialkowski, F. C. E. Tsai, and K. H. Cheng, “UWB switched-beam array antenna employing UWB butler matrix,”in Proceedings of the IEEE International Workshop on Antenna Technology: Small Antennas and Novel Metamaterials (iWAT '08), pp. 199–202, Hsinchu, Taiwan, March 2008. View at Publisher ·View at Google Scholar15J. He, B. Z. Wang, Q. Q. He, Y. X. Xing, and Z. L. Yin, “Wideband x-band microstrip Butler matrix,”Progress in Electromagnetics Rese arch, vol. 74, pp. 131–140, 2007. View at Scopus16Y. Liuqing and G. B. Giannakis, “Ultra wideband communications,”IEEE Signal Proces sing Magazine, vol. 21, no. 6, pp. 26–54, 2004. View at Publisher ·View at Google Scholar ·View at Scopus17S. Banba and H. Ogawa, “Multilayer MMIC directional couplers using thin dielectric layers,” IEEE Transaction s on Micro wave Theory and Techniques, vol. 43, no. 6, pp. 1270–1275, 1995. View at Publisher ·View at Google Scholar ·View at Scopus18J. Sebastien and G. Y. Delisle, “Microstrip EHF butler matrix design and realization,”ETRI Journal, vol. 27, no. 6, pp. 788–797, 2005. View at Scopus19J. H. Cho, H. Y. Hwang, and S. W. Yun, “A design of wideband 3-dB coupler with N-section microstrip tandem structure,” IEEE Microwave and Wireless Components Letters, vol. 15, no. 2, pp. 113–115, 2005. View at Publisher ·View at Google Scholar ·View at Scopus20M. E. Bialkowski, N. Seman, and M. S. Leong, “Design of a compact ultra wideband 3 db microstrip-slot coupler with high return losses and isolation,” in Asia Pacific Microwave Conference (APMC '09), pp. 1334–1337, St. Lucia, Australia, December 2009. View at Publisher ·View at Google Scholar21R. P. Hecken, “A near-optimum matching section without discontinuities,” IEEE Transactions on Microwave Theory and Techniques, vol. 20, no. 11, pp. 734–739, 1972.22 D. M. Pozar, Microwave Engineering, John Wiley& Sons, New York, NY, USA, 2nd edition, 1998.23M. Bona, L. Manholm, J. P. Starski, and B. Svensson, “Low loss compact butler matrix for a microstrip antenna,” IEEE Transactions on Microwave Theory and Techniques, vol. 50, no. 9, pp. 2069–2075, 2002. View at Publisher ·View at Google Scholar24M. Kobayashi and N. Sawada, “Analysis and synthesis of tapered microstrip transmission lines,”IEEE Transactions on Microwave Theory and Techniques, vol. 40, no. 8, pp. 1642–1646, 1992. View at Publisher ·View at Google Scholar宽带非均匀支线耦合器及其应用在宽带巴特勒矩阵的设计与分析协作院校：印尼大学新校区电机工程学系天线传播和微波研究小组（AMRG）。

从简单的ifa到pifa

CST South-East Asia, 21, Jalan Dutamas, 50480, Kuala Lumpur, Malaysia, u@
1. Introduction
When designing a standing wave antenna, the main task is to properly define the resonating elements. With the help of simulation tools such as CST Microwave Studio, these resonating lengths can be identified easily by observing the current and voltage distribution on the antenna. Simulation tools greatly simplify the design effort. Parametric sweeps can be easily done to characterize the behavior of the design, as well to predict the physical dimension of both antenna and ground needed to achieve the desired frequency bands. Printed Inverted-F Antennas (PIFA) are very popular choice of internal antenna for cellular handsets[l]-[5], owing to its ease of design to achieving multiple frequency resonances. When having multiple resonating frequency structure in a single embodiment, tuning of the resonant frequency can be very tricky. Therefore, it is desired to have frequency independent tuning of two or more separate frequencies on a single structure. Once the key control element is identified, tuning can be easily managed. This paper illustrates the design of a multi-band PIFA from a simple IFA.

VIAVI TM500 4G 5G RAN测试设备产品介绍说明书

Continuous monitoring of the RF interface between VIAVI TM500 Test UE(s) and the 4G/5G RAN provides immediate insight into unexpected RF behavior that may impact UE performance. VIAVI Lab to Field TM saves hours of root cause analysis by immediately tracing traffic issues to RF anomalies.There is an expectation that 5G will be an innovation platform that provides the ability to bring new services to market quickly. This will enable service providers to take advantage of market opportunities and dynamically meet changing consumer and business needs. However, deploying and supporting 5G’s complex network architecture will not be a trivial exercise. 5G is causing major changes across the entire network, from RAN architecture to 3Dbeamforming, and active antennas to software-defined network components. All elements need to support stringent application-driven timing and latency requirements. Mission critical applications demand a network which cannot fail, and ensuring network quality will be at the core of deployment. Time-to-market and network quality will depend on the rigor of test and measurement during the complete life cycle of the network. Performing comprehensiveverification during the lab validation stage will ensure a smooth and efficient deployment and launch of the network.Higher order modulation and MIMO schemes such as 256 QAM and 8x8 MIMO are fundamental to delivering the high throughput targets of 5G NR eMBB. Errors introduced at the RF level in the measurement system or due to (e/g)NB failures can lead to missing target throughputs in the lab environment, falsely indicating problems with the (e/g)NB scheduler.BrochureVIAVI Monitor and Troubleshoot 5G RF Channel Performance During Traffic Testing with the Lab to Field Solution5G Devices and Applications Emulation 5G NR Signal/Beam AnalyzerBenefitsy Full 5G NR NSA test coverage from RAN to Corecharacterizes performance with network KPIsy Reliably validate (e/g)NB test configurationprior to starting UE traffic test, increasing testefficiencyy Identify downlink signal stability and beamperformance issues potentially impacting UEresultsy Quickly identify UE performance issues causedby carrier and beam related problemsy Incremental testing approach de-risks validation,reducing time to marketFeaturesy End to end 5G NR testing with configurable dataapplications per UE and 5G Core simulationy Measurement and reporting of available carriersand common beamsy Real-time monitoring of carrier and commonbeam performance indicatorsy Time correlate UE traffic and carrier/beam keyperformance indicatorsy Support for open/closed loop testing, decoupled/coupled UL/DL, low/high-layer test modes2 Monitor and Troubleshoot 5G RF Channel Performance During Traffic Testing with the VIAVI Lab to Field™ Solution3Combined Capability Benefits of TM500 and CellAdvisor 5G for 5G NSA Performance ValidationVIAVI TM500 and CellAdvisor 5G IntroductionVIAVI TM500 is the market leader in lab test UEs and first to market with 5G test solutions. TM500 is the de facto standard in its class, in use with almost every base station manufacturer across the world.y Full Stack 3GPP NSA & SA supporty Sub-6 GHz & mmWave supporting 100 to 200 MHz bandwidthsy eMBB use cases with 4 to 8 carriers and thousands of 5G NR UEsy Multiple antenna configuration support including 2, 4 and 8 layers with up to 256 QAMy Massive MIMO, MU-MIMOVIAVI CellAdvisor™ 5G is the ideal field portable solution to validate 5G radio access. The main test functions listed below validate that signals from the gNB transmitters comply with 3GPP requirements.y Real-time spectrum and interference analysis with persistence display for 5G FR1 (Sub-6 GHz)and FR2 (mmWave)y 5G carrier scanner measuring up to eight 5G carriers’ power as well as strongest beam power leveland corresponding identifier (ID)y 5G beam analyzer measuring individual beams and indicating corresponding identifier, power level,and signal-to-noise ratioy 5G route map for coverage verification, mapping in real time the physical cell identity (PCI) and beam strength, as well as providing coverage data for post-processingCommon Sources of RF Impairments in a Typical Lab EnvironmentDuring normal traffic, RF centric problems will often manifest themselves as a temporary or persistent drop in throughput to the UE. Throughput may also be impacted by problems with the (e/g)NB scheduler, which is totally unrelated to link power or noise, but is a software optimization problem. Being able to quickly identify the RF link as the root cause of a throughput problem means you do not need to investigate the scheduler as a potentialsource of the problem, avoiding a much more complex troubleshooting activity.(e/g)NB Downlink Transmission Errors Modulation MIMO Power LevelIncreased Downlink Errors (BER)Reduced MCS & Modlation/MIMO Order Reduced Throughput Easily assume scheduler causing eMBB throughput issues resulting in complex debug activitySources of Reduced SINR in Measurement SystemDamaged Cables & Loose Connectors High Pathloss Between (e/g)NB & Test UET o avoid these kinds of measurement problems, before using a UE simulator product such as TM500 to execute test cases that may need to run for many hours or even days, it is essential to ensure that RF signals are being received properly, particularly if long cables are needed to connect to the (e/g)NB. 5G adds additional complexity with lab setups requiring multiple TM500 and (e/g)NBs with different bands, sub-carrier spacings and bandwidths up to 100 MHz. In addition, to test mmWave in the lab, mmWave to sub-6 GHz downconverters are often used to facilitate testing in a conducted (cabled) environment.T o ensure that RF signals are being properly received, time consuming pre-verification tests need to be performed when a new system is installed in the lab or while troubleshooting specific tests that are sensitive to changesin the RF signal behavior. The time required for these pre-checks is a major pain point for testers in the lab. The complexity of doing mmWave RF chamber tests can result in these tests being costly, time consuming, and not repeatable.In the rest of the paper we expand on how the TM500 in combination with CellAdvisor 5G can help accelerate these kinds of tests, reduce pain points, and help improve the quality and consistency of results.Accelerate Laboratory Pre-verification ChecksBefore using a UE simulator product such as the TM500, it is essential to ensure that RF signals can be properly received:y The (e/g)NB and UE emulator can be a far distance apart, requiring long cables which can affect power levelsy When the cables are connected, the use of RF attenuators, splitters, and couplers can also affect the power levels and in some cases add noise and reduce the RF signal quality received by the UEy While testing the (e/g)NB it is not guaranteed that the modulation quality and carrier center frequencies are correct and stable, errors that could be due to a faulty setup or erroneous (e/g)NodeB configuration/operation With VIAVI CellAdvisor 5G complementing the TM500, not only can operators and NEMs validate leading 3GPP features with thousands of UEs, but they can also quickly and easily calibrate each setup, do quick pre-checks, and engage in troubleshooting to ensure the RF environment is correct before long duration tests commence.Enhancing and Accelerating Troubleshooting for Signal Quality Sensitive FeaturesWhen the TM500 and (e/g)NB system are set up and running, technicians may need to execute specific tests where results are sensitive to RF signal quality (power level and modulation quality). In particular, this canoften be an issue when a feature is tested for the first time and the expected performance is not obtained. For higher order MIMO such as 4x4 and 8x8, where the power is split between the antennas, small fluctuations inthe RF signal quality at high modulation coding schemes (MCS) can affect the expected data rates. MCS thatuse high modulation schemes such as 256QAM are particularly sensitive to RF signal quality. In the process of troubleshooting, it may be falsely concluded that the (e/g)NB has a scheduler problem, whereas the true root cause is poor signal quality due to low power levels, poor modulation quality, or excessive noise.With VIAVI CellAdvisor 5G, the RF performance of the (e/g)NB can be continuously monitored throughout testing to quickly identify when measured throughput problems are a result of RF issues. This capability, in combination with the leading features supported in the TM500, can reduce troubleshooting time by allowing rapid validation of the quality of the RF signal—including power level and modulation quality—to identify any unexpected impairments that may be impacting signal sensitive tests.4 Monitor and Troubleshoot 5G RF Channel Performance During Traffic Testing with the VIAVI Lab to Field™ SolutionSimplify the Setup of mmWave RF Chamber Tests5G promises the benefit of mmWave technology to allow mobile operators to provide fixed wireless broadband services in enterprise and rural areas. Coupled with Massive MIMO, mmWave presents opportunities that are a viable alternative to fixed cable broadband services. The testing and validation of mmWave and Massive MIMO is, however, complex, costly, and often unreliable in an RF chamber. Ensuring that the chamber horn antennas and converters are positioned correctly to ensure the quality of the signal being received by the TM500 can be time consuming and can benefit from using CellAdvisor 5G for verifying the RF level of each beam and locating the horn antennas at the maximum power point of the beams.One of the challenges of mmWave testing, even in an RF chamber, is to map the beam coverage and quality. In an outdoor environment, CellAdvisor 5G can show a layout of the beam intensity with the assistance of its built-in GPS receiver, which can be connected to a GPS antenna. In an RF chamber, CellAdvisor 5G can measure the different beam strengths at various locations within the chamber. The modulation quality and many other parameters can be checked as well, significantly reducing the time to validate mmWave and beam-forming.Measurement and Reporting of Available Carriers and Common BeamsUtilizing CellAdvisor 5G to quickly validate the 5G NSA lab test setup before starting a traffic profile can detect issues such as poor/broken cable connections and errors with (e/g)NB configuration, allowing these problems tobe corrected before the traffic profile starts. Addressing these problems pre-test eliminates debug associated with failed traffic test cases due to incorrect (e/g)NB configuration. Figure 1 shows a carrier aggregation scenario where path losses are similar for both carriers. All carriers (PCIs of 41, 42, 43, and 44) are showing similar and in range measurements for RF KPIs Channel Power, SS-RSRP, and PBCH-EVM.RF cable connections for a previously good setup can be inadvertently disconnected, loosened, or otherwise impacted. The results of cable connection issues range from a carrier being missing entirely to poor UE performance due to excessive RF noise. UE performance impacts associated with cabling issues are very time consuming to troubleshoot as the root cause is not usually clear based on call processing statistics. CellAdvisor 5G directly measures and identifies key RF KPIs as shown in Figure 2 that are different from other carriers in the setup or out of the expected range, which can quickly identify RF cabling issues or (e/g)NB Downlink RF performance problems without needing to trace them back based on failed traffic statistics.A key feature of CellAdvisor 5G is the beam analyzer. This measurement capability provides the PCI along with SSB Index and measures the SS-RSRP, PS-RSRP, SS-SINR, and SS-RSRQ for the eight strongest beams visible to CellAdvisor 5G. The Beam Analyzer can ensure that all expected common beams are visible to the UE, eliminating problems associated with common beam configuration in the gNB or similar gNB common beam transmission failures.The beam analyzer can also be used to measure the different beam characteristics at various locations within the RF test chamber, ensuring horn antennas are positioned properly to provide the best downlink signal to the test UE.56 Monitor and Troubleshoot 5G RF Channel Performance During Traffic Testing with the VIAVI Lab to Field™ SolutionFigure 1: 5G Carrier aggregation scenario where path losses and signal quality are similar for all carriersFigure 2: Quickly identify carriers with degraded channel power, SS-RSRP, and EVM relative to others in the testFigure 3: Identify the PCI along with SSB Index and the SS-RSRP , PS-RSRP , SS-SINR, and SS-RSRQ for the eight strongest beams7Real-time Monitoring of Carrier and Common Beam Performance IndicatorsFailures in the (e/g)NB can result in brief outages or reductions in performance on a specific carrier or beam which often manifest themselves as a temporary drop in throughput or some related application-specific performance issue. There are many potential causes for a temporary reduction in throughput in a Radio Access Network, some of which are associated with poor downlink RF performance. The real-time carrier monitoring capabilities of CellAdvisor 5G real-time spectrum analyzer, carrier scanner, and beam analyzer allow RF measurements to be continuously recorded in real-time during the execution of a traffic profile. Recorded RF performance information can be evaluated quickly following failure of a test case to help identify the root cause of throughput or other related UE application performance issues when they are caused by problems with the (e/g)NB downlink RF .Figure 4 shows CellAdvisor 5G real-time spectrum analyzer capturing a time gap in the transmission of the downlink signal on one carrier within a multi-carrier 5G setup.Figure 4: Temporary reduction in transmitted RF power on one carrier captured by CellAdvisor 5G persistent spectrogram© 2021 VIAVI Solutions Inc. Product specifications and descriptions in this document are subject to change without notice.Patented as described at /patents lab-to-field-br-nsd-nse-ae 30187648 900 0219C ontact Us +1 844 GO VIAVI (+1 844 468 4284)To reach the VIAVI office nearest you, visit /contact VIAVI Solutions Real-time Spectrum Analyzer Shows RF Signal Over TimeCellAdvisor 5G real-time spectrum analyzer with persistent spectrogram graphically shows utilization of the 5G NR carrier over time. The spectrogram display provides the user with a view across the entire 5G NR carrier of how power is distributed over time. This capability provides insight on which subcarriers and hence resource blocks are preferred by the downlink scheduler. The increased utilization of the lower end of the 5G NR carrier in Figure 5 demonstrates a preference of the gNB to transmit data utilizing these particular sub-carriers.Figure 5: Preference by gNB for resource blocks at lower end of 5G spectrum highlighted by CellAdvisor 5G。

Native Instruments MASCHINE MK3 用户手册说明书

The information in this document is subject to change without notice and does not represent a commitment on the part of Native Instruments GmbH. The software described by this docu-ment is subject to a License Agreement and may not be copied to other media. No part of this publication may be copied, reproduced or otherwise transmitted or recorded, for any purpose, without prior written permission by Native Instruments GmbH, hereinafter referred to as Native Instruments.“Native Instruments”, “NI” and associated logos are (registered) trademarks of Native Instru-ments GmbH.ASIO, VST, HALion and Cubase are registered trademarks of Steinberg Media Technologies GmbH.All other product and company names are trademarks™ or registered® trademarks of their re-spective holders. Use of them does not imply any affiliation with or endorsement by them.Document authored by: David Gover and Nico Sidi.Software version: 2.6.11 (11/2017)Hardware version: MASCHINE MK3Special thanks to the Beta Test Team, who were invaluable not just in tracking down bugs, but in making this a better product.NATIVE INSTRUMENTS GmbH Schlesische Str. 29-30D-10997 Berlin Germanywww.native-instruments.de NATIVE INSTRUMENTS North America, Inc. 6725 Sunset Boulevard5th FloorLos Angeles, CA 90028USANATIVE INSTRUMENTS K.K.YO Building 3FJingumae 6-7-15, Shibuya-ku, Tokyo 150-0001Japanwww.native-instruments.co.jp NATIVE INSTRUMENTS UK Limited 18 Phipp StreetLondon EC2A 4NUUKNATIVE INSTRUMENTS FRANCE SARL 113 Rue Saint-Maur75011 ParisFrance SHENZHEN NATIVE INSTRUMENTS COMPANY Limited 203B & 201B, Nanshan E-Commerce Base Of Innovative ServicesShi Yun Road, Shekou, Nanshan, Shenzhen China© NATIVE INSTRUMENTS GmbH, 2017. All rights reserved.Table of Contents1Welcome to MASCHINE (23)1.1MASCHINE Documentation (24)1.2Document Conventions (25)1.3New Features in MASCHINE 2.6.11 (27)2Basic Concepts (29)2.1Important Names and Concepts (29)2.2Adjusting the MASCHINE User Interface (32)2.2.1Adjusting the Size of the Interface (32)2.2.2Switching between Ideas View and Arranger View (33)2.2.3Showing/Hiding the Browser (34)2.2.4Minimizing the Mixer (34)2.2.5Showing/Hiding the Control Lane (35)2.3Common Operations (36)2.3.1Using the 4-Directional Push Encoder (36)2.3.2Pinning a Mode on the Controller (37)2.3.3Pinning a Mode on the Controller (38)2.3.4Undo/Redo (39)2.3.5List Overlay for Selectors (41)2.3.6Zoom and Scroll Overlays (42)2.3.7Focusing on a Group or a Sound (42)2.3.8Switching Between the Master, Group, and Sound Level (47)2.3.9Navigating Channel Properties, Plug-ins, and Parameter Pages in the Control Area.482.3.9.1Extended Navigate Mode on Your Controller (53)2.3.10Using Two or More Hardware Controllers (56)2.3.11Touch Auto-Write Option (58)2.4Native Kontrol Standard (60)2.5Stand-Alone and Plug-in Mode (62)2.5.1Differences between Stand-Alone and Plug-in Mode (62)2.5.2Switching Instances (63)2.5.3Controlling Various Instances with Different Controllers (64)2.6Preferences (65)2.6.1Preferences – General Page (66)2.6.2Preferences – Audio Page (70)2.6.3Preferences – MIDI Page (74)2.6.4Preferences – Default Page (77)2.6.5Preferences – Library Page (81)2.6.6Preferences – Plug-ins Page (89)2.6.7Preferences – Hardware Page (94)2.6.8Preferences – Colors Page (98)2.7Integrating MASCHINE into a MIDI Setup (100)2.7.1Connecting External MIDI Equipment (100)2.7.2Sync to External MIDI Clock (101)2.7.3Send MIDI Clock (102)2.8Syncing MASCHINE using Ableton Link (103)2.8.1Connecting to a Network (103)2.8.2Joining and Leaving a Link Session (103)2.9Using a Pedal with the MASCHINE Controller (105)2.10File Management on the MASCHINE Controller (105)3Browser (107)3.1Browser Basics (107)3.1.1The MASCHINE Library (107)3.1.2Browsing the Library vs. Browsing Your Hard Disks (108)3.2Searching and Loading Files from the Library (109)3.2.1Overview of the LIBRARY Pane (109)3.2.2Selecting or Loading a Product and Selecting a Bank from the Browser (114)3.2.2.1Browsing by Product Category Using MASCHINE MK3 (118)3.2.2.2Browsing by Product Vendor Using MASCHINE MK3 (119)3.2.3Selecting a Product Category, a Product, a Bank, and a Sub-Bank (119)3.2.3.1Selecting a Product Category, a Product, a Bank, and a Sub-Bank on theController (124)3.2.4Selecting a File Type (125)3.2.5Choosing Between Factory and User Content (126)3.2.6Selecting Type and Mode Tags (127)3.2.7List and Tag Overlays in the Browser (133)3.2.8Performing a Text Search (135)3.2.9Loading a File from the Result List (135)3.3Additional Browsing Tools (140)3.3.1Loading the Selected Files Automatically (140)3.3.2Auditioning Instrument Presets (142)3.3.3Auditioning Samples (143)3.3.4Loading Groups with Patterns (144)3.3.5Loading Groups with Routing (145)3.3.6Displaying File Information (145)3.4Using Favorites in the Browser (146)3.5Editing the Files’ Tags and Properties (152)3.5.1Attribute Editor Basics (152)3.5.2The BANK Page (154)3.5.3The TYPES and MODES Pages (155)3.5.4The PROPERTIES Page (157)3.6Loading and Importing Files from Your File System (158)3.6.1Overview of the FILES Pane (158)3.6.2Using Favorites (160)3.6.3Using the Location Bar (161)3.6.4Navigating to Recent Locations (162)3.6.5Using the Result List (163)3.6.6Importing Files to the MASCHINE Library (166)3.7Locating Missing Samples (168)3.8Using Quick Browse (170)4Managing Sounds, Groups, and Your Project (175)4.1Overview of the Sounds, Groups, and Master (175)4.1.1The Sound, Group, and Master Channels (176)4.1.2Similarities and Differences in Handling Sounds and Groups (177)4.1.3Selecting Multiple Sounds or Groups (178)4.2Managing Sounds (183)4.2.1Loading Sounds (185)4.2.2Pre-listening to Sounds (186)4.2.3Renaming Sound Slots (187)4.2.4Changing the Sound’s Color (187)4.2.5Saving Sounds (189)4.2.6Copying and Pasting Sounds (191)4.2.7Moving Sounds (194)4.2.8Resetting Sound Slots (196)4.3Managing Groups (197)4.3.1Creating Groups (198)4.3.2Loading Groups (200)4.3.3Renaming Groups (201)4.3.4Changing the Group’s Color (201)4.3.5Saving Groups (203)4.3.6Copying and Pasting Groups (205)4.3.7Reordering Groups (208)4.3.8Deleting Groups (209)4.4Exporting MASCHINE Objects and Audio (210)4.4.1Saving a Group with its Samples (211)4.4.2Saving a Project with its Samples (212)4.4.3Exporting Audio (214)4.5Importing Third-Party File Formats (221)4.5.1Loading REX Files into Sound Slots (221)4.5.2Importing MPC Programs to Groups (222)5Playing on the Controller (226)5.1Adjusting the Pads (226)5.1.1The Pad View in the Software (226)5.1.2Choosing a Pad Input Mode (228)5.1.3Adjusting the Base Key (231)5.1.4Using Choke Groups (233)5.1.5Using Link Groups (235)5.2Adjusting the Key, Choke, and Link Parameters for Multiple Sounds (238)5.3Adjusting the Base Key (239)5.4Playing Tools (240)5.4.1Mute and Solo (241)5.4.2Choke All Notes (245)5.4.3Groove (246)5.4.4Level, Tempo, Tune, and Groove Shortcuts on Your Controller (248)5.4.5Tap Tempo (252)5.5Performance Features (253)5.5.1Overview of the Perform Features (253)5.5.2Selecting a Scale and Creating Chords (256)5.5.3Scale and Chord Parameters (256)5.5.4Creating Arpeggios and Repeated Notes (262)5.5.5Swing on Note Repeat / Arp Output (267)5.6Using Lock Snapshots (268)5.6.1Creating a Lock Snapshot (268)5.6.2Using Extended Lock (269)5.6.3Updating a Lock Snapshot (269)5.6.4Recalling a Lock Snapshot (270)5.6.5Morphing Between Lock Snapshots (270)5.6.6Deleting a Lock Snapshot (271)5.6.7Triggering Lock Snapshots via MIDI (272)5.7Using the Smart Strip (274)5.7.1Pitch Mode (274)5.7.2Modulation Mode (275)5.7.3Perform Mode (275)5.7.4Notes Mode (276)6Working with Plug-ins (277)6.1Plug-in Overview (277)6.1.1Plug-in Basics (277)6.1.2First Plug-in Slot of Sounds: Choosing the Sound’s Role (281)6.1.3Loading, Removing, and Replacing a Plug-in (281)6.1.3.1Browser Plug-in Slot Selection (287)6.1.4Adjusting the Plug-in Parameters (290)6.1.5Bypassing Plug-in Slots (290)6.1.6Using Side-Chain (292)6.1.7Moving Plug-ins (292)6.1.8Alternative: the Plug-in Strip (294)6.1.9Saving and Recalling Plug-in Presets (294)6.1.9.1Saving Plug-in Presets (295)6.1.9.2Recalling Plug-in Presets (296)6.1.9.3Removing a Default Plug-in Preset (297)6.2The Sampler Plug-in (298)6.2.1Page 1: Voice Settings / Engine (300)6.2.2Page 2: Pitch / Envelope (302)6.2.3Page 3: FX / Filter (305)6.2.4Page 4: Modulation (307)6.2.5Page 5: LFO (309)6.2.6Page 6: Velocity / Modwheel (311)6.3Using Native Instruments and External Plug-ins (313)6.3.1Opening/Closing Plug-in Windows (313)6.3.2Using the VST/AU Plug-in Parameters (316)6.3.3Setting Up Your Own Parameter Pages (317)6.3.4Using VST/AU Plug-in Presets (322)6.3.5Multiple-Output Plug-ins and Multitimbral Plug-ins (325)7Working with Patterns (326)7.1Pattern Basics (326)7.1.1Pattern Editor Overview (327)7.1.2Navigating the Event Area (333)7.1.3Following the Playback Position in the Pattern (335)7.1.4Jumping to Another Playback Position in the Pattern (337)7.1.5Group View and Keyboard View (338)7.1.6Adjusting the Arrange Grid and the Pattern Length (341)7.1.7Adjusting the Step Grid and the Nudge Grid (344)7.2Recording Patterns in Real Time (349)7.2.1Recording Your Patterns Live (349)7.2.2The Record Prepare Mode (352)7.2.3Using the Metronome (353)7.2.4Recording with Count-in (354)7.2.5Quantizing while Recording (356)7.3Recording Patterns with the Step Sequencer (356)7.3.1Step Mode Basics (356)7.3.2Editing Events in Step Mode (359)7.3.3Recording Modulation in Step Mode (361)7.4Editing Events (361)7.4.1Editing Events with the Mouse: an Overview (362)7.4.2Creating Events/Notes (365)7.4.3Selecting Events/Notes (366)7.4.4Editing Selected Events/Notes (372)7.4.5Deleting Events/Notes (378)7.4.6Cut, Copy, and Paste Events/Notes (381)7.4.7Quantizing Events/Notes (383)7.4.8Quantization While Playing (385)7.4.9Doubling a Pattern (386)7.4.10Adding Variation to Patterns (387)7.5Recording and Editing Modulation (391)7.5.1Which Parameters Are Modulatable? (392)7.5.2Recording Modulation (393)7.5.3Creating and Editing Modulation in the Control Lane (395)7.6Creating MIDI Tracks from Scratch in MASCHINE (401)7.7Managing Patterns (403)7.7.1The Pattern Manager and Pattern Mode (403)7.7.2Selecting Patterns and Pattern Banks (406)7.7.3Creating Patterns (408)7.7.4Deleting Patterns (410)7.7.5Creating and Deleting Pattern Banks (411)7.7.6Naming Patterns (413)7.7.7Changing the Pattern’s Color (415)7.7.8Duplicating, Copying, and Pasting Patterns (416)7.7.9Moving Patterns (419)7.7.10Adjusting Pattern Length in Fine Increments (420)7.8Importing/Exporting Audio and MIDI to/from Patterns (421)7.8.1Exporting Audio from Patterns (421)7.8.2Exporting MIDI from Patterns (422)7.8.3Importing MIDI to Patterns (425)8Audio Routing, Remote Control, and Macro Controls (434)8.1Audio Routing in MASCHINE (435)8.1.1Sending External Audio to Sounds (436)8.1.2Configuring the Main Output of Sounds and Groups (441)8.1.3Setting Up Auxiliary Outputs for Sounds and Groups (446)8.1.4Configuring the Master and Cue Outputs of MASCHINE (450)8.1.5Mono Audio Inputs (456)8.1.5.1Configuring External Inputs for Sounds in Mix View (457)8.2Using MIDI Control and Host Automation (461)8.2.1Triggering Sounds via MIDI Notes (462)8.2.2Triggering Scenes via MIDI (469)8.2.3Controlling Parameters via MIDI and Host Automation (471)8.2.4Selecting VST/AU Plug-in Presets via MIDI Program Change (479)8.2.5Sending MIDI from Sounds (480)8.3Creating Custom Sets of Parameters with the Macro Controls (484)8.3.1Macro Control Overview (485)8.3.2Assigning Macro Controls Using the Software (486)8.3.3Assigning Macro Controls Using the Controller (492)9Controlling Your Mix (494)9.1Mix View Basics (494)9.1.1Switching between Arrange View and Mix View (494)9.1.2Mix View Elements (495)9.2The Mixer (497)9.2.1Displaying Groups vs. Displaying Sounds (498)9.2.2Adjusting the Mixer Layout (500)9.2.3Selecting Channel Strips (501)9.2.4Managing Your Channels in the Mixer (502)9.2.5Adjusting Settings in the Channel Strips (504)9.2.6Using the Cue Bus (508)9.3The Plug-in Chain (510)9.4The Plug-in Strip (511)9.4.1The Plug-in Header (513)9.4.2Panels for Drumsynths and Internal Effects (515)9.4.3Panel for the Sampler (516)9.4.4Custom Panels for Native Instruments Plug-ins (519)9.4.5Undocking a Plug-in Panel (Native Instruments and External Plug-ins Only) (523)9.5Controlling Your Mix from the Controller (525)9.5.1Navigating Your Channels in Mix Mode (526)9.5.2Adjusting the Level and Pan in Mix Mode (527)9.5.3Mute and Solo in Mix Mode (528)9.5.4Plug-in Icons in Mix Mode (528)10Using the Drumsynths (529)10.1Drumsynths – General Handling (530)10.1.1Engines: Many Different Drums per Drumsynth (530)10.1.2Common Parameter Organization (530)10.1.3Shared Parameters (533)10.1.4Various Velocity Responses (533)10.1.5Pitch Range, Tuning, and MIDI Notes (533)10.2The Kicks (534)10.2.1Kick – Sub (536)10.2.2Kick – Tronic (538)10.2.3Kick – Dusty (541)10.2.4Kick – Grit (542)10.2.5Kick – Rasper (545)10.2.6Kick – Snappy (546)10.2.7Kick – Bold (548)10.2.8Kick – Maple (550)10.2.9Kick – Push (551)10.3The Snares (553)10.3.1Snare – Volt (555)10.3.2Snare – Bit (557)10.3.3Snare – Pow (559)10.3.4Snare – Sharp (560)10.3.5Snare – Airy (562)10.3.6Snare – Vintage (564)10.3.7Snare – Chrome (566)10.3.8Snare – Iron (568)10.3.9Snare – Clap (570)10.3.10Snare – Breaker (572)10.4The Hi-hats (574)10.4.1Hi-hat – Silver (575)10.4.2Hi-hat – Circuit (577)10.4.3Hi-hat – Memory (579)10.4.4Hi-hat – Hybrid (581)10.4.5Creating a Pattern with Closed and Open Hi-hats (583)10.5The Toms (584)10.5.1Tom – Tronic (586)10.5.2Tom – Fractal (588)10.5.3Tom – Floor (592)10.5.4Tom – High (594)10.6The Percussions (595)10.6.1Percussion – Fractal (597)10.6.2Percussion – Kettle (600)10.6.3Percussion – Shaker (602)10.7The Cymbals (606)10.7.1Cymbal – Crash (608)10.7.2Cymbal – Ride (610)11Using the Bass Synth (613)11.1Bass Synth – General Handling (614)11.1.1Parameter Organization (614)11.1.2Bass Synth Parameters (616)12Using Effects (618)12.1Applying Effects to a Sound, a Group or the Master (618)12.1.1Adding an Effect (618)12.1.2Other Operations on Effects (627)12.1.3Using the Side-Chain Input (629)12.2Applying Effects to External Audio (632)12.2.1Step 1: Configure MASCHINE Audio Inputs (632)12.2.2Step 2: Set up a Sound to Receive the External Input (635)12.2.3Step 3: Load an Effect to Process an Input (637)12.3Creating a Send Effect (639)12.3.1Step 1: Set Up a Sound or Group as Send Effect (639)12.3.2Step 2: Route Audio to the Send Effect (644)12.3.3 A Few Notes on Send Effects (646)12.4Creating Multi-Effects (647)13Effect Reference (650)13.1Dynamics (651)13.1.1Compressor (651)13.1.2Gate (655)13.1.3Transient Master (659)13.1.4Limiter (661)13.1.5Maximizer (665)13.2Filtering Effects (668)13.2.1EQ (668)13.2.2Filter (671)13.2.3Cabinet (675)13.3Modulation Effects (676)13.3.1Chorus (676)13.3.2Flanger (678)13.3.3FM (680)13.3.4Freq Shifter (681)13.3.5Phaser (683)13.4Spatial and Reverb Effects (685)13.4.1Ice (685)13.4.2Metaverb (687)13.4.3Reflex (688)13.4.4Reverb (Legacy) (690)13.4.5Reverb (692)13.4.5.1Reverb Room (692)13.4.5.2Reverb Hall (695)13.4.5.3Plate Reverb (698)13.5Delays (700)13.5.1Beat Delay (700)13.5.2Grain Delay (703)13.5.3Grain Stretch (705)13.5.4Resochord (707)13.6Distortion Effects (709)13.6.1Distortion (709)13.6.2Lofi (711)13.6.3Saturator (713)13.6.4Analog Distortion (716)13.7Perform FX (718)13.7.1Filter (719)13.7.2Flanger (721)13.7.3Burst Echo (724)13.7.4Reso Echo (726)13.7.5Ring (729)13.7.6Stutter (731)13.7.7Tremolo (734)13.7.8Scratcher (737)14Working with the Arranger (740)14.1Arranger Basics (740)14.1.1Navigating the Arranger (743)14.1.2Following the Playback Position in Your Project (745)14.1.3Jumping to Other Sections (746)14.2Using Ideas View (748)14.2.1Scene Overview (748)14.2.2Creating Scenes (750)14.2.3Assigning and Removing Patterns (751)14.2.4Selecting Scenes (755)14.2.5Deleting Scenes (757)14.2.6Creating and Deleting Scene Banks (758)14.2.7Clearing Scenes (759)14.2.8Duplicating Scenes (759)14.2.9Reordering Scenes (761)14.2.10Making Scenes Unique (762)14.2.11Appending Scenes to Arrangement (763)14.2.12Naming Scenes (764)14.2.13Changing the Color of a Scene (765)14.3Using Arranger View (767)14.3.1Section Management Overview (767)14.3.2Creating Sections (772)14.3.3Assigning a Scene to a Section (773)14.3.4Selecting Sections and Section Banks (774)14.3.5Reorganizing Sections (778)14.3.6Adjusting the Length of a Section (779)14.3.6.1Adjusting the Length of a Section Using the Software (781)14.3.6.2Adjusting the Length of a Section Using the Controller (782)14.3.7Assigning and Removing Patterns (783)14.3.8Duplicating Sections (785)14.3.8.1Making Sections Unique (786)14.3.9Removing Sections (787)14.3.10Renaming Scenes (789)14.3.11Clearing Sections (790)14.3.12Creating and Deleting Section Banks (791)14.3.13Enabling Auto Length (792)14.3.14Looping (793)14.3.14.1Setting the Loop Range in the Software (793)14.4Playing with Sections (794)14.4.1Jumping to another Playback Position in Your Project (795)14.5Triggering Sections or Scenes via MIDI (796)14.6The Arrange Grid (798)14.7Quick Grid (800)15Sampling and Sample Mapping (801)15.1Opening the Sample Editor (801)15.2Recording a Sample (802)15.2.1Opening the Record Page (802)15.2.2Selecting the Source and the Recording Mode (803)15.2.3Arming, Starting, and Stopping the Recording (806)15.2.5Checking Your Recordings (810)15.2.6Location and Name of Your Recorded Samples (813)15.3Editing a Sample (814)15.3.1Using the Edit Page (814)15.3.2Audio Editing Functions (820)15.4Slicing a Sample (828)15.4.1Opening the Slice Page (829)15.4.2Adjusting the Slicing Settings (830)15.4.3Live Slicing (836)15.4.3.1Live Slicing Using the Controller (836)15.4.3.2Delete All Slices (837)15.4.4Manually Adjusting Your Slices (837)15.4.5Applying the Slicing (844)15.5Mapping Samples to Zones (850)15.5.1Opening the Zone Page (850)15.5.2Zone Page Overview (851)15.5.3Selecting and Managing Zones in the Zone List (853)15.5.4Selecting and Editing Zones in the Map View (858)15.5.5Editing Zones in the Sample View (862)15.5.6Adjusting the Zone Settings (865)15.5.7Adding Samples to the Sample Map (872)16Appendix: Tips for Playing Live (875)16.1Preparations (875)16.1.1Focus on the Hardware (875)16.1.2Customize the Pads of the Hardware (875)16.1.3Check Your CPU Power Before Playing (875)16.1.4Name and Color Your Groups, Patterns, Sounds and Scenes (876)16.1.5Consider Using a Limiter on Your Master (876)16.1.6Hook Up Your Other Gear and Sync It with MIDI Clock (876)16.1.7Improvise (876)16.2Basic Techniques (876)16.2.1Use Mute and Solo (876)16.2.2Use Scene Mode and Tweak the Loop Range (877)16.2.3Create Variations of Your Drum Patterns in the Step Sequencer (877)16.2.4Use Note Repeat (877)16.2.5Set Up Your Own Multi-effect Groups and Automate Them (877)16.3Special Tricks (878)16.3.1Changing Pattern Length for Variation (878)16.3.2Using Loops to Cycle Through Samples (878)16.3.3Using Loops to Cycle Through Samples (878)16.3.4Load Long Audio Files and Play with the Start Point (878)17Troubleshooting (879)17.1Knowledge Base (879)17.2Technical Support (879)17.3Registration Support (880)17.4User Forum (880)18Glossary (881)Index (889)1Welcome to MASCHINEThank you for buying MASCHINE!MASCHINE is a groove production studio that implements the familiar working style of classi-cal groove boxes along with the advantages of a computer based system. MASCHINE is ideal for making music live, as well as in the studio. It’s the hands-on aspect of a dedicated instru-ment, the MASCHINE hardware controller, united with the advanced editing features of the MASCHINE software.Creating beats is often not very intuitive with a computer, but using the MASCHINE hardware controller to do it makes it easy and fun. You can tap in freely with the pads or use Note Re-peat to jam along. Alternatively, build your beats using the step sequencer just as in classic drum machines.Patterns can be intuitively combined and rearranged on the fly to form larger ideas. You can try out several different versions of a song without ever having to stop the music.Since you can integrate it into any sequencer that supports VST, AU, or AAX plug-ins, you can reap the benefits in almost any software setup, or use it as a stand-alone application. You can sample your own material, slice loops and rearrange them easily.However, MASCHINE is a lot more than an ordinary groovebox or sampler: it comes with an inspiring 7-gigabyte library, and a sophisticated, yet easy to use tag-based Browser to give you instant access to the sounds you are looking for.What’s more, MASCHINE provides lots of options for manipulating your sounds via internal ef-fects and other sound-shaping possibilities. You can also control external MIDI hardware and 3rd-party software with the MASCHINE hardware controller, while customizing the functions of the pads, knobs and buttons according to your needs utilizing the included Controller Editor application. We hope you enjoy this fantastic instrument as much as we do. Now let’s get go-ing!—The MASCHINE team at Native Instruments.MASCHINE Documentation1.1MASCHINE DocumentationNative Instruments provide many information sources regarding MASCHINE. The main docu-ments should be read in the following sequence:1.MASCHINE Getting Started: This document provides a practical approach to MASCHINE viaa set of tutorials covering easy and more advanced tasks in order to help you familiarizeyourself with MASCHINE.2.MASCHINE Manual (this document): The MASCHINE Manual provides you with a compre-hensive description of all MASCHINE software and hardware features.Additional documentation sources provide you with details on more specific topics:▪Controller Editor Manual: Besides using your MASCHINE hardware controller together withits dedicated MASCHINE software, you can also use it as a powerful and highly versatileMIDI controller to pilot any other MIDI-capable application or device. This is made possibleby the Controller Editor software, an application that allows you to precisely define all MIDIassignments for your MASCHINE controller. The Controller Editor was installed during theMASCHINE installation procedure. For more information on this, please refer to the Con-troller Editor Manual available as a PDF file via the Help menu of Controller Editor.▪Online Support Videos: You can find a number of support videos on The Official Native In-struments Support Channel under the following URL: https:///NIsupport-EN We recommend that you follow along with these instructions while the respective appli-cation is running on your computer.Other Online Resources:If you are experiencing problems related to your Native Instruments product that the supplied documentation does not cover, there are several ways of getting help:▪Knowledge Base▪User Forum▪Technical Support▪Registration SupportYou will find more information on these subjects in the chapter Troubleshooting.1.2Document ConventionsThis section introduces you to the signage and text highlighting used in this manual. This man-ual uses particular formatting to point out special facts and to warn you of potential issues. The icons introducing these notes let you see what kind of information is to be expected:This document uses particular formatting to point out special facts and to warn you of poten-tial issues. The icons introducing the following notes let you see what kind of information can be expected:Furthermore, the following formatting is used:▪Text appearing in (drop-down) menus (such as Open…, Save as… etc.) in the software and paths to locations on your hard disk or other storage devices is printed in italics.▪Text appearing elsewhere (labels of buttons, controls, text next to checkboxes etc.) in the software is printed in blue. Whenever you see this formatting applied, you will find the same text appearing somewhere on the screen.▪Text appearing on the displays of the controller is printed in light grey. Whenever you see this formatting applied, you will find the same text on a controller display.▪Text appearing on labels of the hardware controller is printed in orange. Whenever you see this formatting applied, you will find the same text on the controller.▪Important names and concepts are printed in bold.▪References to keys on your computer’s keyboard you’ll find put in square brackets (e.g.,“Press [Shift] + [Enter]”).►Single instructions are introduced by this play button type arrow.→Results of actions are introduced by this smaller arrow.Naming ConventionThroughout the documentation we will refer to MASCHINE controller (or just controller) as the hardware controller and MASCHINE software as the software installed on your computer.The term “effect” will sometimes be abbreviated as “FX” when referring to elements in the MA-SCHINE software and hardware. These terms have the same meaning.Button Combinations and Shortcuts on Your ControllerMost instructions will use the “+” sign to indicate buttons (or buttons and pads) that must be pressed simultaneously, starting with the button indicated first. E.g., an instruction such as:“Press SHIFT + PLAY”means:1.Press and hold SHIFT.2.While holding SHIFT, press PLAY and release it.3.Release SHIFT.Unlabeled Buttons on the ControllerThe buttons and knobs above and below the displays on your MASCHINE controller do not have labels.1234567812345678The unlabeled buttons and knobs on the MASCHINE controller.For better reference, we applied a special formatting here: throughout the document, the ele-ments are capitalized and numbered, so the buttons above the displays are written Button 1 to Button 8, while the knobs under the displays are written Knob 1 to Knob 8. E.g., whenever you see an instruction such as “Press Button 2 to open the EDIT page,” you’ll know it’s the second button from the left above the displays.1.3New Features in MASCHINE2.6.11The following two new features have been added to MASCHINE 2.6.11 and are only aimed at MASCHINE MK3 users:▪Introduction of the General, Audio, MIDI and Hardware Preferences direct from the MA-SCHINE MK3 controller using the SETTINGS button. For more information on using the Preferences from the hardware, refer to each section of the following chapter: ↑2.6, Prefer-ences.。

EFR32xG28双频子GHz和2.4 GHz设计要求说明书

AN1409: EFR32xG28 Sub-GHz and 2.4 GHz Dual-Band Requirements The EFR32xG28 chip family provides sub-GHz and 2.4 GHz dual-band functionality that requires special design considerations. This application note provides guidance on how to utilize both the sub-GHz and 2.4 GHz port of the device, and shows recommen-ded matching networks and layout for both bands.Note: This document does not address detailed matching procedures. The 2.4 GHz matching procedure is described in application note AN930.2: EFR32 Series 2 2.4 GHz Matching Guide. The sub-GHz matching procedure is described in application note, AN923.2: EFR32 Series 2 sub-GHz Matching Guide. For more detailed information on PCB layout requirements for proper operation, refer to application note, AN928.2:EFR32 Series 2 Layout Design Guide.KEY FEATURES•Provides instructions on how to design dual-band devices•Specifically discusses the 868/915 MHz + 2.4 GHz use case•Recommended matching networks for both bands•Layout design considerations for dual-band applicationsTable of Contents1. Recommended Matching Networks (3)1.1 Sub-GHz Match Networks (3)1.2 2.4 GHz matching network (4)1.3 Special Case: 868/915 MHz + 2.4 GHz Dual-Band Matching Network (5)1.3.1 Application Schematic For 868/915 MHz Dual Band RF Matching (7)1.3.2 RF Switch Parameters (8)1.3.3 RF Switch Special Layout Considerations (8)2. Reference Designs (9)3. Revision History (10)1. Recommended Matching NetworksFor the sub-GHz bands in the range of 169 - 470 MHz, no special precautions are needed. Both sub-GHz and 2.4 GHz ports can be used with the matching networks shown below, with separate antennas for each band.For the 868/915 MHz band, an RF switch is needed to ground the end of the 2.4 GHz matching path to minimize the coupling of the 3rd harmonic of the sub-GHz frequency to the 2.4 GHz antenna when transmitting at 868/915 MHz.Note: All the parts recommended below are in SMD0201 footprint size.1.1 Sub-GHz Match NetworksFigure 1.1. Typicl Sub-GHz FR Matching Network CircuitTable 1.1. Summary of Matching Network Component Values vs. Frequency1.22.4 GHz matching networkFigure 1.2. 2.4 GHz RF Matching Network CircuitTable 1.2. 2.4 GHz Matching Network Component Values1.3 Special Case: 868/915 MHz +2.4 GHz Dual-Band Matching NetworkThis dual-band board setup needs attention, because the 3rd harmonic of the sub-GHz band can be radiated out from the 2.4 GHz antenna, due to the coupling of the 3rd harmonic of the sub-GHz band to the 2.4 GHz path (especially, through the bonding wires). The 3rd harmonic of 868/915 MHz is at 2.6 – 2.7 GHz, close to the other path’s fundamental frequency of 2.4 GHz, so that path does not attenuate it.Figure 1.3. 3rd Harmonic Coupling at 868 MHz 14 dBmThe solution is to add an external RF switch to connect the output of the 2.4 GHz matching network to ground, through 50 Ω, when using the sub-GHz RF front-end. This switch will be activated before a sub-GHz transmission starts, so the path through the 2.4 GHz matching network will be terminated before the 2.4 GHz antenna input.IF THE SOLUTION BELOW IS NOT IMPLEMENTED, THE SYSTEM WILL FAIL FCC RESTRICTED BAND REQUIREMENTS!Figure 1.4. Solution to 3rd Harmonic Coupling at 868 MHz 14 dBm1.3.1 Application Schematic For 868/915 MHz Dual Band RF MatchingFigure 1.5. 868/915 MHz +14 dBm Dual Band Matching with Ground Switch for 2.4 GHz +10 dBmFigure 1.6. 868/915 MHz +20 dBm Dual Band Matching with Ground Switch for 2.4 GHz +10 dBm1.3.2 RF Switch ParametersIf the switch recommended by Silicon Labs may not be available, here are the requirements for a replacement:•Minimal Insertion Loss at 2.4 GHz (~0.3-0.4 dB)•One control pin• 3 RF Ports (RFIN, RF1, RF2)•Max Input Power >= 10dBm•At least 25 dB isolation between ports1.3.3 RF Switch Special Layout Considerations•Use DC blocking capacitors, if needed (the one used in Radio Board reference designs does not need DC blocking)•RF Switches need low-impedance ground connection, so ground vias at the exposed pad or any other grounding pin are neces-sary •Place the 50 Ω load as close as possible•If another RF switch is chosen (with higher non-linearity) then TX output filtering after the switch may be neededFigure 1.7. RF Switch Layout for Dual Band MatchingReference Designs 2. Reference Designs•BRD4400B: EFR32xG28 868/915 MHz 14 dBm + 2.4 GHz 10 dBm Radio Board with active RF switch•BRD4400C: EFR32xG28 868/915 MHz 14 dBm + 2.4 GHz 10 dBm Radio Board with passive RF switch•BRD4401B: EFR32xG28 868/915 MHz 20 dBm + 2.4 GHz 10 dBm Radio Board with active RF switch•BRD4401C: EFR32xG28 868/915 MHz 20 dBm + 2.4 GHz 10 dBm Radio Board with passive RF switchRevision History 3. Revision HistoryRevision 0.1August 2023•Initial draftIoT Portfolio /products Quality /quality Support & Community /communitySilicon Laboratories Inc.400 West Cesar Chavez Austin, TX 78701USA DisclaimerSilicon Labs intends to provide customers with the latest, accurate, and in-depth documentation of all peripherals and modules available for system and software imple-menters using or intending to use the Silicon Labs products. Characterization data, available modules and peripherals, memory sizes and memory addresses refer to each specific device, and “Typical” parameters provided can and do vary in different applications. Application examples described herein are for illustrative purposes only. Silicon Labs reserves the right to make changes without further notice to the product information, specifications, and descriptions herein, and does not give warranties as to the accuracy or completeness of the included information. Without prior notification, Silicon Labs may update product firmware during the manufacturing process for security or reliability reasons. Such changes will not alter the specifications or the performance of the product. Silicon Labs shall have no liability for the consequences of use of the infor -mation supplied in this document. This document does not imply or expressly grant any license to design or fabricate any integrated circuits. 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Silicon Labs is replacing these terms with inclusive language wherever possible. For more information, visit /about-us/inclusive-lexicon-projectTrademark InformationSilicon Laboratories Inc.®, Silicon Laboratories ®, Silicon Labs ®, SiLabs ® and the Silicon Labs logo ®, Bluegiga ®, Bluegiga Logo ®, EFM ®, EFM32®, EFR, Ember ®, Energy Micro, Energy Micro logo and combinations thereof, “the world’s most energy friendly microcontrollers”, Redpine Signals ®, WiSeConnect , n-Link, ThreadArch ®, EZLink ®, EZRadio ®, EZRadioPRO ®, Gecko ®, Gecko OS, Gecko OS Studio, Precision32®, Simplicity Studio ®, Telegesis, the Telegesis Logo ®, USBXpress ® , Zentri, the Zentri logo and Zentri DMS, Z-Wave ®, and others are trademarks or registered trademarks of Silicon Labs. ARM, CORTEX, Cortex-M3 and THUMB are trademarks or registered trademarks of ARM Holdings. Keil is a registered trademark of ARM Limited. Wi-Fi is a registered trademark of the Wi-Fi Alliance. 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REFERENCES
[ I ] V. Radisic, Yongxi Qian, and Tatsuo Itoh, "Novel Architectures for HighEfficiency Amplifiers for Wireless Applications", IEEE Trans. MIT, vol. 46, No. 11,Nov.pp. 1901-1909, 1998. [2] V. Radisic, Siou Teck Chew, Yongxi Qian and Tatsuo Itoh, "High-efficiency power amplifier integrated with antenna", IEEE Microwave and Guided Wave Letters, vol. 72, Feb., pp. 39-41, 1997 [3] S. Maci, G. Biffi Gentili, P. Piauesi, and C. Salvador, "Dual-band slotloaded patch antenna," Microwaves, Antennas and Propagation, IEE Proceedings, vol. 142 Issue 3, June, pp. 225 -232, 1995
high efficiency and low cost. One of them is the harmonic tuning antenna research for the power amplifier integrated antenna system[l]. In this active integrated antenna system, it can reduce the harmonic filter and matching network that is used by conventional system. The harmonic tuning antenna have been used for EM1 reduction and improving PAE such as short-pin antenna for 2nd harmonic tuning, sector antenna for 3rd harmonic tuning, and short-pin PBG for both 2nd and 3rd harmonics[lJ[2]. The PAE can be improved by optimizing the load impedance at the fundamental and by optimally loading the harmonics[2]. However, short-pin antenna cannot suppress 3rd harmonic and the sector antenna has a cross polarization problem. PBG structure has low gain and needs large dimension. Also, slot loaded antenna can be used for the 3rd harmonic tuning as well as for dual frequency operation[3]. In this paper, rectangular slots and short-pins loaded antenna for 2nd and 3rd harmonic tuning are presented. The operation frequency of the antenna is 5.77GHz for ITS services in Korea.
SIMULATED RESULTS
Simulated results of input resistance versus frequency and radiation characteristics for the proposed design in Fig. I are presented. Fig. 2 shows the input resistance versus frequency for the proposed antenna and conventional rectangular antenna. It shows that the proposed antenna provides 2.751 in 2nd harmonics and 1 I f 2 in 3rd harmonics. Also the simulated CO- and crosspolarization radiation patterns in E- and H-plane of the antenna are illustrated in Fig.3. The radiation patterns are simulated at the resonant frequency, 2nd and 3rd harmonics. The cross-polarization levels in the fundamental frequency are lower than -30 dB.
120
U0
m
(a) E-plane
(b)e
(d) H-plane
(e) E-plane
(0H-plane
Fig. 3 The simulated radiation patterns for the proposed antenna, (a) (b) f = 5.77GHz.(c)(d)f= 11.54GHz,(e)(f) f = 17.31CHz
INTRODUCTION
As advances in wireless communication technology are taken very rapidly, there have been many researches for active integrated antennas in order to get
0-7803-7070-8/01/$10.00 02001 IEEE
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This antenna is etched on TLX-9-0200 substrate having relative permittivity (Er) 2.5, thickness 0.508mm. The designed antenna parameters are summarized in Table 1.
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Table I . The designed antenna parameters
v'
Fig.1 Geometry of rectangular microstrip antenna using slots and short-pins
10
Frequensy(GHr)
15
20
Fig. 2 The simulated resistance versus frequency for the proposed antenna and rectangular patch antenna
ANTENNA DESIGNS
Fig. I shows the geometry of the proposed antenna. The proposed system is designed to obtain harmonic tuning characteristics using slots and short-pins. For integrating power amplifier, the microstrip feeding method for a matching network will be removed. Short-pins along the centerline of the patch can make a voltage zero along the centerline and not affecting fundamental and 3rd harmonic frequencies, and slot along the radiating edge can affect 3rd harmonic. But the perturbation effect is weak on the fundamental frequency and the resonant frequency flo is rarely shifted. To use the microstrip line feed, slots are composed of two parts.
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CONCLUSIONS
Recently active integrated antennas are studied for more efficiency and harmonic reduction. The designed antenna provides a good radiation pattern on resonant frequency, and reduces EM1 by suppression of 2"d and 3rdharmonics. Also it increases PAE on power amplifier integrated antenna by operating as shorting loads on harmonics. *This work was supported by grant No. 2000-2-0632 from the Basic Research Program of the Korea Science & Engineering Foundation.