NCP1203功能介绍
NCP1203D6应用电路
Cbulk
HV
UVLO
Vcc CVcc
Laux
High-Voltage Technology
Half-wave connection Only 27% in gain /
APEC-exhibitor-sem-ON February 2004
9
Suppose we want to start-up in 250ms with: CVcc = 22µF, UVLO = 12V Istartup total (IC + capacitor) = 50µA Universal mains input, 100 – 370VDC 12⋅22µ A 250ms time sequence imposes a current of: i= =1mA 250m • Standard connection: R = (100-12)/1m=88kΩ 2 ÆP@370VDC = 1.55W! ( Vbulk ) P= Rstartup • Half-wave connection: 28kΩ 2 ÆP@370VDC = 1.22W! ( Vac) P= 2⋅Rstartup • High-voltage technology: ÆIsource = 4mA, then startup time equals 66ms P=35µ⋅VDC ÆP@370VDC = 13mW!
100.0M
0
315.4U
882.7U
1.450M
2.017M
2.585M
Cycle skipping in standby Low peak current!
NCP120X
APEC-exhibitor-sem-ON February 2004
NCP1230,MC33262数据手册参数说明及电路应用
Simulated
Measured
Winning Feature Set
ON Semiconductor offers a wide variety of controllers with features to fit your application:
~ Fixed frequency current or voltage mode topologies ~ Variable-frequency Quasi-Resonant (QR) and resonant mode
~ High speed and high accuracy control with high voltage switching on a single die
~ Power switching devices scalable from 200 Volts to over 1000 Volts
IEC 1000-3-2 standards set regulations to limit the harmonics injected into the AC line by any equipment drawing more than 75 W of input power for class D equipment (TV sets, PC monitors, desktop PCs) and 25 W for class C equipment (lighting). A front-end Power Factor Controller is then required in these power supplies. Adding such a stage can lead to difficulties in meeting other regulatory requirements (standby and active power) unless you make judicious design choices.
液晶电源IC的代换资料 2
格式如下好了"
液晶品牌与型号 电源管理芯片型号与封装 可代换型号
qBENQ 71G+ 1200AP40 直插 1200AP10 1200AP60
AOC 712SI EA1532A贴片
三星型号忘记 DM0565R
203D6 NCP1203D60R2 NCP1203D60R2G和DAP8A 直接代换
DAP02ALSZ与SG6841S可以互换
1200AP40和1200AP60直接代换
P5S0765和DP104、DP704直接代换
DP804和DP904直接代换
2S0680和2S0880直接代换
美格WB9D7575PS5
清华同方 XP911WD7575PS
联想LXM -WL19AH LXM-WL19BH D7575PS(早期有的用：NCP1203D6)
联想LXM-17CH:1203D6
方正17寸：1203D6与LD7575PS
方正19寸：LD7575PS
BenQ: FP94VW FP73G FP71G+S FP71G+G FP71GX等都是用：1200AP40
TEA1507和TEA1533直接代换
LD7535兼容 SG6848 (6849) / SG5701 / SG5848 /LD7535 (7550) / OB2262 (2263) / OB2278（2279）RS2051
LD7575和NCP1203、NCP1200 OB2268 SG5841 LD7552 OB2269 OB2268 RS20429
CR6850兼容SG6848/6849/5701/5848,OB2262/2263,LD7550/7535.
USB-1203产品说明书
USB-120316路12位AD，2路12位DA，16路DIO，2路24位脉冲记数，2路24位PWM输出板用户使用手册北京新超仁达科技有限公司2011．7二、概述 (4)三、主要特点、性能 (4)四、原理说明 (5)4.1、逻辑框图 (5)4.2、工作原理简述 (5)五、使用 (6)5.1、JP3、JP4：AD输入量程选择 (6)5.2、A/D注意事项 (6)5.3、JP1、JP2：DA输出量程选择 (6)5.4、D/A注意事项： (6)5.5、ID设置：（四位拨码开关SW设置） (6)5.6、测频原理 (7)5.7、PWM输出原理 (8)六、引脚定义 (9)6.1、模拟输入输出引脚定义 (9)6.2、数字量输入输出、脉冲输入、脉冲输出引脚定义 (10)七、电位器功能与输出码制对应关系 (10)7.1、四个电位器RW1、RW2、RW3、RW4，功能：调整A/D (10)7.2、两个电位器RW5、RW6功能：调整D/A (11)7.3、输出码制对应关系 (11)7.3.1、模拟量输入的数据格式 (11)7.3.2、码制 (11)八、常用信号的连接、处理 (12)8.1、模拟输入低通滤波： (12)8.2、模式的电流/电压变换： (12)8.3、外部模拟输入信号的接法： (13)8.4、数字量输出接法： (13)九、软件 (13)USB-1203的软件包括USB-1203驱动程序，动态链接库及调用例程。
(13)9.1、驱动安装 (13)9.2、测试程序 (16)9.3、函数调用说明 (16)9.4、DLL函数全部是WINAPI调用约定的，即_stdcall接口 (21)9.5、关于USB1203.dll位置的说明 (22)9.6、驱动文件 (22)十、编程指导 (22)10.1、VC程序编程说明 (22)10.2、VB程序编程说明 (23)10.3、LabVIEW程序编程说明 (23)10.4、LabWindows/CVI编程说明 (23)10.5、Delphi程序编程说明 (23)十一、维修服务 (24)11.1产品完整性 (24)11.2维修 (24)11.3服务 (24)USBUSB--1203多功能卡一、前言信息社会的发展，在很大程度上取决于信息与信号处理技术的先进性。
AC.DC控制IC的杰作——NCP1200系列IC介绍
AC/DC控制IC的杰作——NCP1200系列IC介绍今年美国ONSEMI公司新推出的为AC/DC交流适配器设计的电流型准谐振式PWM控制IC，将近年来半导体的高科技及PWM IC的高科技集成在一起创造了最优秀的电源控制器系列，其代表产品为NCP1207。
NCP1207为电流型控制准谐振工作的控制IC。
输出的驱动信号由峰值电流设置点来决定其给出输出驱动信号还是关断。
并由磁复位检测到的工作状态来开启。
它共有7个引脚，每个都决定着IC控制的关键参数。
首先它通过磁复位检测确保电源工作在反激变换式断续导通型边缘，准谐振状态。
这样可以使主功率MOSFET工作于零电压开关的软开关状态，即ZVS状态，使功率MOS无开关损耗。
变压器二次侧若用二极管整流，则二极管无反向恢复损耗。
IC的供电采用动态自供电方式（DSS）。
它将内部集成的高压DMOS的漏极（8pin）直接接高压总线,并组成一个高压恒流源供给接在IC 6pin的电解电容充电，当充电电压达到12V时IC开始工作，并有驱动脉冲输出(5pin)。
而当6pin电压低于10V时输出关断。
对于驱动小功率MOSFET时,电容上的能量基本够用，可不必外接Vcc。
对于驱动功率较大的MOSFET时,需要再接入Vcc的供电绕组补充能量，以维持其在10V以上的电平,保持IC能正常工作。
NCP1207还有很好的极低的空载功耗的维持能力。
它采用的是跳跃周期工作形式。
在输出功率低于给定水平时，NCP1207进入自动跨跃开关周期的工作方式。
这是用监视IC的2pin FB端子电平来实现的。
IC正常工作时，2pin上给一个峰值电流，其值取决于负载。
如果负载减小，峰值电流即变小，当其达到设置点水平时，IC即开始消隐输出脉冲。
此时IC进入跨跃周期工作型。
当输出电压下跌到某一点时，输出再重新进入正常工作。
这就有效地保持了空载损耗很低的优点。
其跨越周期的长短还可以用一颗电阻去调整，以便达到最低空载功耗。
LCD电源芯片代换
S0765和DP104、DP704直接代换
DP804和DP904直接代换
2S0680和2S0880直接代换
TEA1507和TEA1533直接代换
DAP8A,DAP7A,LD7575,203D6,203X6,200D6可以直接代换
203d6是16v工作电压，而7575是30v ,代用要改启动电阻，
FAN7601与LAF0001可以直接代换
EA1532A可以用DAP8A
203D6代换 P1337要把一脚启动电阻由18k换成100k
OCP5001-TL5001直接代换
AMC3100-LTC3406/AT1366/直接代换
MP2104 OCP2150-LTC3406/直接代换
AT1366/MP2104 直接代换
DAP02可用SG5841 。SG6841代换: EA1530 EA1532
TOP246Y可用TOP247Y代
1200AP40和1200AP60直接换，我用1200AP40代过1203P605S0765和DP104、DP704、DP706直接代换
我用DP704代过8S0765C不过加了个24V的稳压二极管
LD7575和NCP1203、NCP1200 OB2268 SG5841 LD7552 OB2269 OB2268 RS2042
CR6860兼容ACT30，
CR6853兼容OB2263,
CR6201兼容THX201，TFC718；
CR6202兼容THX202，TFC719；
CR6203兼容THX203，TFC718S。
DP804和DP904直接代换
2S0680和2S0880直接代换
PWM开关电源芯片1203P60
NCP1203PWM Current−Mode Controller for UniversalOff−Line Supplies Featuring Standby and Short Circuit ProtectionHoused in SOIC−8 or PDIP−8 package, the NCP1203 represents a major leap toward ultra−compact Switchmode Power Supplies and represents an excellent candidate to replace the UC384X devices. Due to its proprietary SMARTMOS t Very High V oltage Technology, thecircuit allows the implementation of complete off−line AC−DC adapters, battery charger and a high−power SMPS with few external components.With an internal structure operating at a fixed 40 kHz, 60 kHz or 100 kHz switching frequency, the controller features a high−voltage startup FET which ensures a clean and loss−less startup sequence. Its current−mode control naturally provides good audio−susceptibility and inherent pulse−by−pulse control.When the current setpoint falls below a given value, e.g. the output power demand diminishes, the IC automatically enters the so−called skip cycle mode and provides improved efficiency at light loads while offering excellent performance in standby conditions. Because this occurs at a user adjustable low peak current, no acoustic noise takes place.The NCP1203 also includes an efficient protective circuitry which, in presence of an output over load condition, disables the output pulses while the device enters a safe burst mode, trying to restart. Once the default has gone, the device auto−recovers. Finally, a temperature shutdown with hysteresis helps building safe and robust power supplies.Features•Pb−Free Packages are Available•High−V oltage Startup Current Source•Auto−Recovery Internal Output Short−Circuit Protection •Extremely Low No−Load Standby Power•Current−Mode with Adjustable Skip−Cycle Capability •Internal Leading Edge Blanking•250 mA Peak Current Capability•Internally Fixed Frequency at 40 kHz, 60 kHz and 100 kHz •Direct Optocoupler Connection•Undervoltage Lockout at 7.8 V Typical•SPICE Models Available for TRANsient and AC Analysis •Pin to Pin Compatible with NCP1200Applications•AC−DC Adapters for Notebooks, etc.•Offline Battery Chargers•Auxiliary Power Supplies (USB, Appliances, TVs, etc.)SOIC−8D1, D2 SUFFIXCASE 7511MARKINGDIAGRAMSPIN CONNECTIONSPDIP−8N SUFFIXCASE 6268xx= Specific Device CodeA= Assembly LocationWL, L= Wafer LotY, YY= YearW, WW= Work WeekAdj HVFBCSGNDNCV CCDrv(Top View)xxxxxxxxxAWLYYWW18See detailed ordering and shipping information in the package dimensions section on page 12 of this data sheet.ORDERING INFORMATION查询1203P60供应商Figure 1. Typical Application ExampleV OUTPIN FUNCTION DESCRIPTIONFigure 2. Internal Circuit ArchitectureMAXIMUM RATINGSMaximum ratings are those values beyond which device damage can occur. Maximum ratings applied to the device are individual stress limit values (not normal operating conditions) and are not valid simultaneously. If these limits are exceeded, device functional operation is not implied, damage may occur and reliability may be affected.ELECTRICAL CHARACTERISTICS (For typical values T J = 25°C, for min/max values T J = 0°C to +125°C, Max T J = 150°C,J2.Maximum value @ T J = 25°C, please see characterization curves.3.Pin 5 loaded by 1 nF.TEMPERATURE (°C)1251007550250−25150200250300350400I C C @ V C C = 6 V (m A )Figure 3. V CC(on) Threshold versusTemperatureFigure 4. V CC(min) Level versus Temperature8.48.2−258.07.67.2125−2514.013.85012.612.412.21007.42525125TEMPERATURE (°C)TEMPERATURE (°C)V C C (m i n ) L E V E L (V )V C C (o n ) T H R E S H O L D (V )7513.012.813.213.613.450751007.8Figure 5. I C Current Consumption (No Load)versus Temperature Figure 6. I CC Consumption (Loaded by 1 nF)versus TemperatureTEMPERATURE (°C)Figure 7. HV Current Source at V CC = 10 Vversus Temperature Figure 8. I C Consumption at V CC = 6 Vversus TemperatureTEMPERATURE (°C)TEMPERATURE (°C)5005506006507007509501000I C C , C U R R E N T C O N S U M PT I O N (m A )800850900 1.01.21.41.61.82.0I C C ,1 n F L O A D C O N S U M P T I O N (m A )4.04.55.05.56.06.57.58.07.0H V C U R R E N T S O U R C E (m A )6050252015D R I V E S O U R C E R E S I S T A N C E (W )30354540Figure 11. Maximum Current Setpoint versusTemperatureFigure 12. Frequency versus Temperature0.990.970.890.870.85TEMPERATURE (°C)TEMPERATURE (°C)M A X I M U M C U R R E N T S E T P O I N T (V )0.910.930.9555APPLICATION INFORMATIONIntroductionThe NCP1203 implements a standard current mode architecture where the switch−off time is dictated by the peak current setpoint. This component represents the ideal candidate where low part−count is the key parameter,particularly in low−cost AC−DC adapters, auxiliary supplies etc. Due to its high−performance SMARTMOS High−V oltage technology, the NCP1203 incorporates all the necessary components normally needed in UC384X based supplies: timing components, feedback devices, low−pass filter and startup device. This later point emphasizes the fact that ON Semiconductor’s NCP1203 does not need an external startup resistance but supplies the startup current directly from the high−voltage rail. On the other hand, more and more applications are requiring low no−load standby power, e.g. for AC−DC adapters, VCRs etc. UC384X series have a lot of difficulty to reduce the switching losses at low power levels. NCP1203 elegantly solves this problem byskipping unwanted switching cycles at a user−adjustable power level. By ensuring that skip cycles take place at low peak current, the device ensures quiet, noise free operation.Finally, an auto−recovery output short−circuit protection (OCP) prevents from any lethal thermal runaway in overload conditions.Startup SequenceWhen the power supply is first powered from the mains outlet, the internal current source (typically 6.0 mA) is biased and charges up the V CC capacitor. When the voltage on this V CC capacitor reaches the V CC(on) level (typically 12.8 V), the current source turns off and no longer wastes any power. At this time, the V CC capacitor only supplies the controller and the auxiliary supply is supposed to take over before V CC collapses below V CC(min). Figure 13 shows the internal arrangement of this structure:Figure 13. The Current Source Brings V CC Above 12.8 V and then Turns OffAux12.8 V/4.9 VOnce the power supply has started, the V CC shall be constrained below 16 V , which is the maximum rating on pin 6. Figure 14 portrays a typical startup sequence with a V CC regulated at 12.5 V:Figure 14. A Typical Startup Sequence forthe NCP1203t, TIME (sec)13.512.511.510.59.5Current−Mode OperationAs the UC384X series, the NCP1203 features a well−known current mode control architecture which provides superior input audio−susceptibility compared to traditional voltage−mode controllers. Primary current pulse−by−pulse checking together with a fast over current comparator offers greater security in the event of a difficult fault condition, e.g. a saturating transformer.Adjustable Skip Cycle LevelBy offering the ability to tailor the level at which the skip cycle takes place, the designer can make sure that the skip operation only occurs at low peak current. This point guarantees a noise−free operation with cheap transformers. Skip cycle offers a proven mean to reduce the standby power in no or light loads situations.Wide Switching−Frequency OfferFour different options are available: 40 kHz − 65 kHz –100 kHz. Depending on the application, the designer can pick up the right device to help reducing magnetics or improve the EMI signature before reaching the 150 kHz starting point.Overcurrent Protection (OCP)When the auxiliary winding collapses below UVLOlow, the controller stops switching and reduces its consumption. It stays in this mode until Vcc reaches 4.9 V typical, where the startup source is reactivated and a new startup sequence is attempted. The power supply is thus operated in burst mode and avoids any lethal thermal runaway. When the default goes way, the power supply automatically resumes operation.Wide Duty−Cycle OperationWide mains operation requires a large duty−cycle excursion. The NCP1203 can go up to 80% typically.Low Standby PowerIf SMPS naturally exhibit a good efficiency at nominal load, they begin to be less efficient when the output power demand diminishes. By skipping un−needed switching cycles, the NCP1203 drastically reduces the power wasted during light load conditions. In no−load conditions, the NCP1203 allows the total standby power to easily reach next International Energy Agency (IEA) recommendations.No Acoustic Noise while OperatingInstead of skipping cycles at high peak currents, the NCP1203 waits until the peak current demand falls below a user−adjustable 1/3rd of the maximum limit. As a result, cycle skipping can take place without having a singing transformer … You can thus select cheap magnetic components free of noise problems.External MOSFET ConnectionBy leaving the external MOSFET external to the IC, you can select avalanche proof devices which, in certain cases (e.g. low output powers), let you work without an active clamping network. Also, by controlling the MOSFET gate signal flow, you have an option to slow down the device commutation, therefore reducing the amount of ElectroMagnetic Interference (EMI).SPICE ModelA dedicated model to run transient cycle−by−cycle simulations is available but also an averaged version to help you closing the loop. Ready−to−use templates can be downloaded in OrCAD’s Pspice and INTUSOFT’s from ON Semiconductor web site, NCP1203 related section. Overload OperationIn applications where the output current is purposely not controlled (e.g. wall adapters delivering raw DC level), it is interesting to implement a true short−circuit protection. A short−circuit actually forces the output voltage to be at a low level, preventing a bias current to circulate in the optocoupler LED. As a result, the auxiliary voltage also decreases because it also operates in Flyback and thus duplicates the output voltage, providing the leakage inductance between windings is kept low. To account for this situation and properly protect the power supply, NCP1203 hosts a dedicated overload detection circuitry. Once activated, this circuitry imposes to deliver pulses in a burst manner with a low duty−cycle. The system auto−recovers when the fault condition disappears.During the startup phase, the peak current is pushed to the maximum until the output voltage reaches its target and the feedback loop takes over. The auxiliary voltage takes place after a few switching cycles and self−supplies the IC. In presence of a short circuit on the output, the auxiliary voltage will go down until it crosses the undervoltage lockout level of typically 7.8 V. When this happens, NCP1203 immediately stops the switching pulses and unbias all unnecessary logical blocks. The overall consumption drops, while keeping the gate grounded, and the V CC slowly falls down. As soon as V CC reaches typically 4.8 V, the startup source turns−on again and a new startup sequence occurs, bringing V CC toward 12.8 V as an attempt to restart. If the default has gone, then the power supply normally restarts. If not, a new protective burst is initiated, shielding the SMPS from any runaway. Figure 15, on the following page, portrays the typical operating signals in short circuit.Figure 15. Typical Waveforms in Short Circuit Conditions7.8 V12.8 V4.9 VV CCDRIVING PULSESCalculating the V CC CapacitorThe V CC capacitor can be calculated knowing the IC consumption as soon as V CC reaches 12.8 V . Suppose that a NCP1203P60 is used and drives a MOSFET with a 30 nC total gate charge (Qg). The total average current is thus made of ICC1 (700 m A) plus the driver current, Fsw x Qg or 1.8 mA. The total current is therefore 2.5 mA. The D V available to fully startup the circuit (e.g. never reach the 7.8 V UVLO during power on) is 12.8–7.8 = 5 V . We have a capacitor who then needs to supply the NCP1203 with 2.5 mA during a given time until the auxiliary supply takes over. Suppose that this time was measured at around 15 ms.CV CC is calculated using the equation C +D t ·i D VorC w 7.5m F . Select a 22 m F/16 V and this will fit.Skipping Cycle ModeThe NCP1203 automatically skips switching cycles when the output power demand drops below a given level. This is accomplished by monitoring the FB pin. In normal operation, pin 2 imposes a peak current accordingly to the load value. If the load demand decreases, the internal loop asks for less peak current. When this setpoint reaches a determined level (Vpin 1), the IC prevents the current from decreasing further down and starts to blank the output pulses: the IC enters the so−called skip cycle mode, also named controlled burst operation. The power transfer now depends upon the width of the pulse bunches (Figure 17).Suppose we have the following component values:Lp, primary inductance = 350 m H Fsw , switching frequency = 61 kHz Ip skip = 600 mA (or 333 mV/Rsense)The theoretical power transfer is therefore:12·Lp ·Ip 2·Fsw +3.8W If this IC enters skip cycle mode with a bunch length of 10 ms over a recurrent period of 100 ms, then the total power transfer is: 3.8.0.1+380mW .To better understand how this skip cycle mode takes place,a look at the operation mode versus the FB level immediately gives the necessary insight:Figure 16.When FB is above the skip cycle threshold (1.0 V by default), the peak current cannot exceed 1.0 V/Rsense.When the IC enters the skip cycle mode, the peak current cannot go below Vpin1/3.3/Rsense. The user still has the flexibility to alter this 1.0 V by either shunting pin 1 to ground through a resistor or raising it through a resistor up to the desired level. Grounding pin 1 permanently invalidates the skip cycle operation. However, given the extremely low standby power the controller can reach, the PWM in no−load conditions can quickly enter the minimum t on and still transfer too much power. An instability can take place. We recommend in that case to leave a little bit of skip level to always allow 0% duty cycle.Power P1Power P2Power P3Figure 17. Output Pulses at Various Power Levels (X = 5.0 m s/div) P1 t P2 t P3Figure 18. The Skip Cycle Takes Place at Low Peak Currents which Guaranties Noise−Free Operation315.40882.70 1.450 M 2.017 M 2.585 M300 M200 M100 MWe recommend a pin 1 operation between 400 mV and 1.3 V that will fix the skip peak current level between 120 mV/Rsense and 390 mV/Rsense.Non−Latching ShutdownIn some cases, it might be desirable to shut off the part temporarily and authorize its restart once the default hasdisappeared. This option can easily be accomplished through a single NPN bipolar transistor wired between FB and ground. By pulling FB below the Adj pin 1 level, the output pulses are disabled as long as FB is pulled below pin 1. As soon as FB is relaxed, the IC resumes its operation.Figure 19 depicts the application example.Figure 19. Another Way of Shutting Down the IC without a Definitive Latch−Off StateFull Latching ShutdownOther applications require a full latching shutdown, e.g.when an abnormal situation is detected (overtemperature or overvoltage). This feature can easily be implemented through two external transistors wired as a discrete SCR.When the V CC level exceeds the zener breakdown voltage,the NPN biases the PNP and fires the equivalent SCR,permanently bringing down the FB pin. The switching pulses are disabled until the user unplugs the power supply.Figure 20. Two Bipolars Ensure a Total Latch−Off of the SMPS in Presence of an OVPLAuxRhold 0.1 m Rhold ensures that the SCR stays on when fired. The bias current flowing through Rhold should be small enough to let the V CC ramp up (12.8 V) and down (4.9 V) when the SCR is fired. The NPN base can also receive a signal from a temperature sensor. Typical bipolars can be MMBT2222and MMBT2907 for the discrete latch. The MMBT3946features two bipolars NPN+PNP in the same package and could also be used.Protecting the Controller Against Negative SpikesAs with any controller built upon a CMOS technology, it is the designer’s duty to avoid the presence of negative spikes on sensitive pins. Negative signals have the bad habit to forward bias the controller substrate and induce erratic behaviors. Sometimes, the injection can be so strong that internal parasitic SCRs are triggered, engendering irremediable damages to the IC if they are a low impedance path is offered between V CC and GND. If the current sensepin is often the seat of such spurious signals, the high−voltage pin can also be the source of problems in certain circumstances. During the turn−off sequence, e.g.when the user un−plugs the power supply, the controller is still fed by its V CC capacitor and keeps activating the MOSFET ON and OFF with a peak current limited by Rsense. Unfortunately, if the quality coefficient Q of the resonating network formed by Lp and Cbulk is low (e.g. the MOSFET Rdson + Rsense are small), conditions are met to make the circuit resonate and thus negatively bias the controller. Since we are talking about ms pulses, the amount of injected charge (Q = I x t) immediately latches the controller which brutally discharges its V CC capacitor. If this V CC capacitor is of sufficient value, its stored energy damages the controller. Figure 21 depicts a typical negative shot occurring on the HV pin where the brutal V CC discharge testifies for latchup.Figure 21. A negative spike takes place on the Bulk capacitor at the switch−off sequenceSimple and inexpensive cures exist to prevent from internal parasitic SCR activation. One of them consists in inserting a resistor in series with the high−voltage pin to keep the negative current to the lowest when the bulk becomes negative (Figure 22). Please note that the negative spike is clamped to –2 x Vf due to the diode bridge. Also, the power dissipation of this resistor is extremely small since it only heats up during the startup sequence.Another option (Figure 23) consists in wiring a diode from V CC to the bulk capacitor to force V CC to reach UVLOlow sooner and thus stops the switching activity before the bulk capacitor gets deeply discharged. For security reasons, two diodes can be connected in series.Figure 22. A simple resistor in series avoids anylatchup in the controllerCV CCD31N4007CV CCRbulk > 4.7 kFigure 23. or a diode forces V CC to reachUVLOlow sooner†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specifications Brochure, BRD8011/D.D1, D2 SUFFIX CASE 751−07ISSUE AC*For additional information on our Pb−Free strategy and solderingdetails, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.SOLDERING FOOTPRINT*NOTES:1.DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982.2.CONTROLLING DIMENSION: MILLIMETER.3.DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION.4.MAXIMUM MOLD PROTRUSION 0.15 (0.006)PER SIDE.5.DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBARPROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION.6.751−01 THRU 751−06 ARE OBSOLETE. NEW STANDARD IS 751−07.DIM A MIN MAX MIN MAX INCHES4.805.000.1890.197MILLIMETERS B 3.80 4.000.1500.157C 1.35 1.750.0530.069D 0.330.510.0130.020G 1.27 BSC 0.050 BSC H 0.100.250.0040.010J 0.190.250.0070.010K 0.40 1.270.0160.050M 0 8 0 8 N 0.250.500.0100.020S5.806.200.2280.244YM0.25 (0.010)Z SXS____ǒmm inchesǓSCALE 6:1N SUFFIX CASE 626−05ISSUE LNOTES:1.DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL.2.PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS).3.DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982.DIM MIN MAX MIN MAX INCHESMILLIMETERS A 9.4010.160.3700.400B 6.10 6.600.2400.260C 3.94 4.450.1550.175D 0.380.510.0150.020F 1.02 1.780.0400.070G 2.54 BSC 0.100 BSC H 0.76 1.270.0300.050J 0.200.300.0080.012K 2.92 3.430.1150.135L 7.62 BSC 0.300 BSC M −−−10 −−−10 N0.76 1.010.0300.040__ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates,and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.PUBLICATION ORDERING INFORMATIONThe product described herein (NCP1203), may be covered by the following U.S. patents: 6,271,735, 6,362,067, 6,385,060, 6,429,709, 6,587,357. There may be other patents pending.SMARTMOS is a trademark of Motorola, Inc.。
液晶常用电源管理芯片
1200AP40 1200AP60、1203P60200D6、203D6 DAP8A 可互代203D6/1203P6 DAP8A2S0680 2S08803S0680 3S08805S0765 DP104、DP7048S0765C DP704加24V得稳压二极管ACT4060 ZA3020LV/MP1410/MP9141ACT4065 ZA3020/MP1580ACT4070 ZA3030/MP1583/MP1591MP1593/MP1430ACT6311 LT1937ACT6906 LTC3406/A T1366/MP2104AMC2576 LM2576AMC2596 LM2596AMC3100 LTC3406/AT1366/MP2104AMC34063A AMC34063AMC7660 AJC1564AP8012 VIPer12AAP8022 VIPer22ADAP02 可用SG5841 /SG6841代换DAP02ALSZ SG6841DAP02ALSZ SG6841DAP7A、DP8A 203D6、1203P6DH321、DL321 Q100、DM0265RDM0465R DM/CM0565RDM0465R/DM0565R 用cm0565r代换(取掉4脚得稳压二极管) DP104 5S0765DP704 5S0765DP706 5S0765DP804 DP904FAN7601 LAF0001LD7552 可用SG6841代(改4脚电阻)LD7575PS 203D6改1脚100K电阻为24KOB2268CP OB2269CPOB2268CP SG6841改4脚100K电阻为2047KOCP1451 TL1451/BA9741/SP9741/AP200OCP2150 LTC3406/AT1366/MP2104OCP2160 LTC3407OCP2576 LM2576OCP3601 MB3800OCP5001 TL5001OMC2596 LM2596/AP1501PT1301 RJ9266PT4101 AJC1648/MP3202PT4102 LT1937/AJC1896/AP1522/RJ9271/MP1540SG5841SZ SG6841DZ/SG6841DSM9621 RJ9621/AJC1642SP1937 LT1937/AJC1896/AP1522/RJ9271/MP1540STRG5643D STRG5653D、STRG8653DTEA1507 TEA1533TEA1530 TEA1532对应引脚功能接入THX202H TFC719THX203H TFC718STOP246Y TOP247YV A7910 MAX1674/75 L6920 AJC1610VIPer12A VIPer22A[audio01]ICE2A165(1A/650V、31W);ICE2A265(2A/650V、52W);ICE2B0565(0、5A/650V、23W):ICE2B165(1A/650V、31W);ICE2B265(2A/650V、52W);ICE2A180(1A/800V、29W);ICE2A280(2A/800、50W)、KA5H0365R, KA5M0365R, KA5L0365R, KA5M0365RN# u) t! u1 W1 B) R, PKA5L0365RN, KA5H0380R, KA5M0380R, KA5L0380R1、KA5Q1265RF/RT(大小两种体积)、KA5Q0765、FSCQ1265RT、KACQ1265RF、FSCQ0765RT、FSCQ1565Q这就是一类得,这些型号得引脚功能全都一样,只就是输出功率不一样。
PSL620C技术说明书V4.3
国电南自Q/GDNZ.J.01.72-2000标准备案号：1539- 2000PSL 620C系列数字式线路保护技术说明书国电动份GUODIAN NANJING AUTOMATION CO.，LTDPSL620C数字式线路保护装置技术说明书V4.30国电南京自动化股份有限公司2005年12月版本声明本技术说明书适用于以下版本的保护程序：PSL621C距离保护版本： 4.53PSL621C零序重合闸保护版本： 4.52PSL622C高频保护版本： 4.10PSL623C过流零序重合闸保护版本： 4.53PSL626C过流距离重合闸保护版本： 2.82PSL627C过流重合闸保护版本： 2.82产品说明书版本修改记录表1098765432 V4.3 增加具备双以太网通信口(或三以太网)、RS485串行通信口、V4.52 2005.12 就地打印串行通讯口、PSView调试分析软件串行通讯口1 V4.0 增加装置整体结构图、面板布置图、结构安装图等 V4.50 2003.9 序号 说明书版本修 改 摘 要 软件版本号 修改日期* 技术支持：电话（025）51183140传真（025）51183144* 本说明书可能会被修改，请注意核对实际产品与说明书的版本是否相符* 2005年12月 第1版 第1次印刷目 录1 概述 (1)1.1适用范围 (1)1.2功能配置及型号 (1)1.3性能特点 (1)2 技术性能及指标 (3)2.1额定电气参数 (3)2.2技术性能及指标 (3)2.3环境条件 (4)2.4绝缘性能 (4)2.5电磁兼容性能 (5)2.6机械性能 (5)3 PSL621C线路保护装置 (6)3.1功能及原理 (6)3.1.1 启动元件 (6)3.1.2 选相元件 (6)3.1.3 距离保护 (6)3.1.4 零序保护 (12)3.1.5 重合闸继电器 (14)3.1.6 失灵启动 (16)3.1.7 合闸加速保护 (16)3.1.8 交流电压电流异常判断 (17)3.1.9 过流保护 (18)3.1.10 低周减载、低压减载 (18)3.2硬件构成 (20)3.2.1 硬件配置 (20)3.2.2 各模件说明 (22)3.3定值与整定 (31)3.3.1 装置整定项目与有关参数整定范围 (31)3.3.2 整定计算及整定方法简介 (33)4 PSL622C线路保护装置 (37)4.1功能及原理 (37)4.1.1 高频保护 (37)4.2硬件构成 (44)4.2.1 硬件配置 (44)4.2.2 各模件说明 (45)4.3定值与整定 (46)4.3.1 装置整定项目与有关参数整定范围 (46)4.3.2 整定计算及整定方法简介 (47)5 PSL623C线路保护装置 (49)5.1功能及原理 (49)5.2硬件构成 (50)5.2.1 硬件配置 (50)5.2.2 各模件说明 (51)5.3定值与整定 (52)5.3.1 装置整定项目与有关参数整定范围 (52)5.3.2 整定计算及整定方法简介 (54)6 PSL626C 线路保护装置 (56)6.1功能及原理 (56)6.2硬件构成 (60)6.2.1 硬件配置 (60)6.2.2 各模件说明 (61)6.3定值与整定 (65)6.3.1 装置整定项目与有关参数整定范围 (65)6.3.2 整定计算及整定方法简介 (66)7 PSL627C 线路保护装置 (69)7.1功能及原理 (69)7.2硬件构成 (70)7.2.1 硬件配置 (70)7.2.2 各模件说明 (71)7.3定值清单及整定说明 (72)7.3.1 装置整定项目与有关参数整定范围 (72)7.3.2 整定计算及整定方法简介 (73)8 信息记录和分析 (75)9 与变电站自动化系统配合 (75)10 事件信息一览表 (76)1 概述1.1 适用范围PSL 620C系列数字式线路保护装置是以距离保护、零序保护和三相一次重合闸为基本配置的成套线路保护装置，并集成了电压切换箱和三相操作箱，适用于110KV、66KV或35KV输配电线路。
安森美产品系列
可调跳周期 与锁存
结构图
软跳周期 基于定时器短路 保护
双打嗝式故障 负载瞬态检测器
补偿斜坡 热关断
最大占空比 限制
频率 抖动
8
Hui Yu 2007.5.23
启动与软启动
9
Hui Yu 2007.5.23
内置启动 FET
反激辅助线圈在正常条件下提供偏置 电压以降低能耗
15
Hui Yu 2007.5.23
斜坡电流 Iramp
斜坡电流是三角形电流，80% 的开关周期内从 0 uA 上升到 100 uA 。 该电流通过低于 1000 Ω 的电阻 Rramp （如 500 Ω ），在调制中将补 偿斜坡施加到 VCS 上。这可提高电流模式调节的稳定性。 如 Rramp 为零，则 uA 级斜坡电流仅通过低于1 Ω 的电阻 RCS（如 0.2 Ω ），这样补偿斜坡会非常小，可以忽略不计。
☺ 启动顺序良好， ☺
☺
☺ 无噪声 ☺从无负载到正常
无损耗 减少元件数量
工作模式快速恢复
☺ 提高设计 ☺ 适合占空比 ☺ 减少元件 降低 灵活性 大于 50% MOSFET 数量 （可用于各种） 的应用 压力及噪声 ☺ 安全可靠的 保护机制 元件
设计灵活性
更小的低成 本滤波器
市场与应用
• • •
消费类电子产品 (DVD 播放器、机顶盒、电视机等) PSU 适配器 开放式电源
√
23V 无 √ 无 18 V 7.7～12.6 V （典型值） 500 mA 800 mA 无 内部
√
165°C （典型值） SOIC8、SOIC7 及 PDIP-7
5
Hui Yu 2007.5.23
液晶电源管理芯片型号与封装代换型号
液晶品牌与型号电源管理芯片型号与封装可代换型号xaslipyelBENQ 71G+1200AP40 直插1200AP10 1200AP60AOC 712SI EA1532A贴片xaslipyel三星940BW DM0565Rxaslipyel优派型号忘记 TOP245YNxaslipyelLG W1934S TOP246YNxaslipyel飞利浦170s6 dap02alsz 贴片xaslipyelLG型号忘记 LAF0001 可以用FAN7601代xaslipyel飞利浦170s6 dap02alsz=sg6841xaslipyelHP17驱动高压电源全一体 SG5841SZ贴片，可用SG6841DZ 代用。
xaslipyel联想后来出的像IBM的 17的，SG6841DZ 可用SG6841D代用xaslipyel三星型号忘记 DM0465R(我记得还有这么一款的)xaslipyel飞利浦170c7 EA1532A贴片xaslipyel200D6、203D6、DAP8A 三种可以代用xaslipyel优派VA1703WB ld7552bps 贴片xaslipyel其他我知道的常用型号有xaslipyelSG6841DZ 贴片很多机器上用到xaslipyelSG5841SZ 贴片用SG6841DZ可以代用，xaslipyel美格WB9 LD7575PS清华同方 XP911W LD7575PS联想LXM -WL19AH LXM-WL19BH LD7575PS(早期有的用：NCP1203D6)联想LXM-17CH: 1203D6方正17寸：1203D6与LD7575PS方正19寸：LD7575PSBenQ: FP94VW FP73G FP71G+S FP71G+G FP71GX等都是用：1200AP40 LG 22(南京同创）：LAF001与STR W6252 。
LG 19寸：LAF001 联想L193(福建-捷联代工）：NCP1203D6PHILIPS 170S5 (FAN7601)还有LD7575可用203D6代用，只是1脚的对地电阻不同，LD7575是100K,203D6是24.1K,LP7552可用SG6841代用希望大家都列下来，这样子备PWM IC的时候就有个数了，知道买什么样子的电源管理芯片备用着，有时候手上没有，知道是电源管理坏了在那里干着急，反正PWM IC便宜的，可以每样备个2个，以备不时之需介绍几个ＬＣＤ液晶显示器电源ＩＣ的代换希望能帮上大家．ＤＡＰ８Ａ＼ＤＡＰ７Ａ＼ＬＤ７５７５＼２０３Ｄ６可以直接代换ＤＡＰ０２＼ＳＧ５８４１＼SＧ６８４１可以直接代换１２００ＡＰ４０＼１２００ＡＰ６０＼１２０３Ｐ６０可以直接代换ＤＭ０４６５R＼ＣＭ０５６５R＼ＤＭ０５６５R可以直接代换ＴＯＰ２４６Ｙ＼ＴＯＰ２４７Ｙ可以直接代换常见显示器IC代换OCP5001-----------TL5001AMC3100----------LTC3406/AT1366/MP2104 OCP2150----------- LTC3406/AT1366/MP2104 ACT6906----------- LTC3406/AT1366/MP2104 OCP2160-----------LTC3407AMC34063A-----------AMC34063AMC7660------------AJC1564ACT4060--------------ZA3020LV/MP1410/MP9141ACT4065------------ZA3020/MP1580ACT4070----------ZA3030/MP1583/MP1591MP1593/MP1430 AMC2576-------LM2576AMC2596-------LM2596OCP2576--------LM2576OMC2596-------LM2596/AP1501VA7910---------MAX1674/75 L6920 AJC1610SM9621---------RJ9621/AJC1642PT1301----------RJ9266PT4101----------AJC1648/MP3202PT4102----------LT1937/AJC1896/AP1522/RJ9271/MP1540 ACT6311-------LT1937SP1937-----------LT1937/AJC1896/AP1522/RJ9271/MP1540 OCP3601---------MB3800OCP1451---------TL1451/BA9741/SP9741/AP200电源IC STR-G5643D G5653D G8653D 直接代换203D6和DAP8A 直接代换1200AP40和1200AP60直接代换5S0765和DP104、DP704直接代换DP804和DP904直接代换2S0680和2S0880直接代换TEA1507和TEA1533直接代换三星的DP104,704,804可以用5S0765代换,DP904不能用任何块代换行场振荡、场输出、视频ICTDA9109和SID2511、KB2511、STV7779直接代换TDA9103和STV7778直接代换TDA9112和TDA9113直接代换TDA9115和TDA9116、STV6888直接代换TDA9118和STV9118直接代换TDA8172和TDA9302、TDA8177直接代换TDA1675 和DBL2056直接代换TDA9210和STV9210直接代换LM1203和LM2203、DBL2054直接代换TDA9116用STV6888代换,TDA4856可以用TDA4841PS代换,TDA9112可以用TDA9113代换,S1D2511可以用TDA9109代换２０３Ｄ６２００Ｄ６ＬＤ７５７５ＤＡＰ８Ａ２０３Ｘ６直接代换ＳＧ６８４１ＳＧ５８４１ＤＡＰＯ２直接代换ＤＭ0456 ＤＭ０５６５直接代换１２００ＡＰ４０１２００ＡＰ６０１２０３ＡＰ１０直接代。
NCP1203D6应用电路
Cbulk
HV
UVLO
Vcc CVcc
Laux
High-Voltage Technology
Half-wave connection Only 27% in gain /
APEC-exhibitor-sem-ON February 2004
9
Suppose we want to start-up in 250ms with: CVcc = 22µF, UVLO = 12V Istartup total (IC + capacitor) = 50µA Universal mains input, 100 – 370VDC 12⋅22µ A 250ms time sequence imposes a current of: i= =1mA 250m • Standard connection: R = (100-12)/1m=88kΩ 2 ÆP@370VDC = 1.55W! ( Vbulk ) P= Rstartup • Half-wave connection: 28kΩ 2 ÆP@370VDC = 1.22W! ( Vac) P= 2⋅Rstartup • High-voltage technology: ÆIsource = 4mA, then startup time equals 66ms P=35µ⋅VDC ÆP@370VDC = 13mW!
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Driving Efficient Power Solutions from Standby to Active Mode (from line to load)
Dhaval Dalal Technical Marketing Director
XN1203_CN 1.3
Vin=110V,Io=1A
Vin=220V,Io=0.5A
Vin=220V,Io=1A
◎西安英洛华微电子有限公司 DS.XN1203 V1.3
第5页
2011 年 05 月
XN1203 电流模式 PWM 开关电源控制器
Vin=265V,Io=0.5A
Vin=265V,Io=1A
2. 输出噪声波形 Vin=85V,Io=1A
-
-
0.2
输出噪声电压
F=10Hz-10KHz
-
-
长期稳定性
T=85℃条件下工作1000h
-
5
振荡器部分
振荡频率
Ct=680PF
55
66
频率随电压变化率
Vcc=5.5V-9.0V
-
-
频率随温度变化率
Ta=0-85℃
-
-
振荡器振幅
-
-
2.5
振荡器下降沿
Ct=680PF
-
900
反馈部分
输入阻抗
上拉电流
0.5
5. 启动时的 Vce 和 Vo 波形 Vin=85V,Io=1A
Vin=265V,Io=1A
6. 输出短路时的 Vce 波形 Vin=85V,Io=1A
电路内部结构框图
Vin=265V,Io=1A
◎西安英洛华微电子有限公司 DS.XN1203 V1.3
第7页
2011 年 05 月
工作原理
XN1203 电流模式 PWM 开关电源控制器
IS OC
管脚定义描述
功率管基极，启动电流输入，外接启动电阻 供电脚 接地脚
振荡电容脚，外接定时电容 反馈脚
开关电流取样与限制设定，外接电流取样电阻 输出脚，接开关变压器
xn1203
IC 具有带迟滞的欠电压保护功能。在 VCC 电压达 到 9.6V 时 IC 开始启动，这个初始的启动电压有驱 动电阻提供，输入的高电压通过驱动电阻注入开关 管的基极，放大的 IC 电流在 IC 内部经过限制电路 对 VCC 电容充电，从而形成驱动电压。在 IC 正常 工作时应保持 VCC 电压在 4.8-9V 之间（包括满负 载输出的情况），若 VCC 电压下降到 4.4V 则振荡 器将进入关闭状态，VCC 进一步降低到 3.6V 时， IC 即开始重新启动。IC 内部 VCC 具有一个上限电 压比较器控制，若 VCC 试图大于 10.5V，则比较器 动作，FB 将被下拉，锁定 VCC 至 10.5V，达到过 电压的限制功能。利用此功能可以方便的实现前端 的电压反馈功能，也可避免输出开环时的输出电压 大幅度升高现象，保障负载的安全。因为此特性的 存在，VCC 的设计应保持在合适的范围，避免在大 输出负载时 VCC 的上升过高，IC 过压限制动作导 致输出电压下降现象。
CL=1nF
输出下降时间输出限制电流Fra bibliotek540
580
◎西安英洛华微电子有限公司 DS.XN1203V2.0
第3页
最大
1 75 75 620
单位
V V ns ns mA
2009 年 1 月
XN1203 高性能电流模式 PWM 开关电源控制器
OE 钳位电压
OE=0.001-0.29A
-
1.5
-
V
振荡器部分
特点
关断周期发射极偏压输出，提高了功率管的 耐压
内置具有温度补偿的电流限制电阻，精确电 流限制
内置热保护电路 利用开关功率管完成启动，使启动电阻的功
耗减少 10 倍以上 极少的外围元器件 低启动和工作电流 VCC 过压自动限制 宽电压输出功率可达 12W，窄电压输出功率
NCP1203P100中文资料
NCP1203PWM Current−Mode Controller for UniversalOff−Line Supplies Featuring Standby and Short Circuit ProtectionHoused in SOIC−8 or PDIP−8 package, the NCP1203 represents a major leap toward ultra−compact Switchmode Power Supplies and represents an excellent candidate to replace the UC384X devices. Due to its proprietary SMARTMOS t Very High V oltage Technology, thecircuit allows the implementation of complete off−line AC−DC adapters, battery charger and a high−power SMPS with few external components.With an internal structure operating at a fixed 40 kHz, 60 kHz or 100 kHz switching frequency, the controller features a high−voltage startup FET which ensures a clean and loss−less startup sequence. Its current−mode control naturally provides good audio−susceptibility and inherent pulse−by−pulse control.When the current setpoint falls below a given value, e.g. the output power demand diminishes, the IC automatically enters the so−called skip cycle mode and provides improved efficiency at light loads while offering excellent performance in standby conditions. Because this occurs at a user adjustable low peak current, no acoustic noise takes place.The NCP1203 also includes an efficient protective circuitry which, in presence of an output over load condition, disables the output pulses while the device enters a safe burst mode, trying to restart. Once the default has gone, the device auto−recovers. Finally, a temperature shutdown with hysteresis helps building safe and robust power supplies.Features•Pb−Free Packages are Available•High−V oltage Startup Current Source•Auto−Recovery Internal Output Short−Circuit Protection •Extremely Low No−Load Standby Power•Current−Mode with Adjustable Skip−Cycle Capability •Internal Leading Edge Blanking•250 mA Peak Current Capability•Internally Fixed Frequency at 40 kHz, 60 kHz and 100 kHz •Direct Optocoupler Connection•Undervoltage Lockout at 7.8 V Typical•SPICE Models Available for TRANsient and AC Analysis •Pin to Pin Compatible with NCP1200Applications•AC−DC Adapters for Notebooks, etc.•Offline Battery Chargers•Auxiliary Power Supplies (USB, Appliances, TVs, etc.)SOIC−8D1, D2 SUFFIXCASE 7511MARKINGDIAGRAMSPIN CONNECTIONSPDIP−8N SUFFIXCASE 6268xx= Specific Device CodeA= Assembly LocationWL, L= Wafer LotY, YY= YearW, WW= Work WeekAdj HVFBCSGNDNCV CCDrv(Top View)xxxxxxxxxAWLYYWW18See detailed ordering and shipping information in the package dimensions section on page 12 of this data sheet.ORDERING INFORMATIONFigure 1. Typical Application ExampleV OUTPIN FUNCTION DESCRIPTIONFigure 2. Internal Circuit ArchitectureMAXIMUM RATINGSMaximum ratings are those values beyond which device damage can occur. Maximum ratings applied to the device are individual stress limit values (not normal operating conditions) and are not valid simultaneously. If these limits are exceeded, device functional operation is not implied, damage may occur and reliability may be affected.ELECTRICAL CHARACTERISTICS (For typical values T J = 25°C, for min/max values T J = 0°C to +125°C, Max T J = 150°C,J2.Maximum value @ T J = 25°C, please see characterization curves.3.Pin 5 loaded by 1 nF.TEMPERATURE (°C)1251007550250−25150200250300350400I C C @ V C C = 6 V (m A )Figure 3. V CC(on) Threshold versusTemperatureFigure 4. V CC(min) Level versus Temperature8.48.2−258.07.67.2125−2514.013.85012.612.412.21007.42525125TEMPERATURE (°C)TEMPERATURE (°C)V C C (m i n ) L E V E L (V )V C C (o n ) T H R E S H O L D (V )7513.012.813.213.613.450751007.8Figure 5. I C Current Consumption (No Load)versus Temperature Figure 6. I CC Consumption (Loaded by 1 nF)versus TemperatureTEMPERATURE (°C)Figure 7. HV Current Source at V CC = 10 Vversus Temperature Figure 8. I C Consumption at V CC = 6 Vversus TemperatureTEMPERATURE (°C)TEMPERATURE (°C)5005506006507007509501000I C C , C U R R E N T C O N S U M PT I O N (m A )800850900 1.01.21.41.61.82.0I C C ,1 n F L O A D C O N S U M P T I O N (m A )4.04.55.05.56.06.57.58.07.0H V C U R R E N T S O U R C E (m A )6050252015D R I V E S O U R C E R E S I S T A N C E (W )30354540Figure 11. Maximum Current Setpoint versusTemperatureFigure 12. Frequency versus Temperature0.990.970.890.870.85TEMPERATURE (°C)TEMPERATURE (°C)M A X I M U M C U R R E N T S E T P O I N T (V )0.910.930.9555APPLICATION INFORMATIONIntroductionThe NCP1203 implements a standard current mode architecture where the switch−off time is dictated by the peak current setpoint. This component represents the ideal candidate where low part−count is the key parameter,particularly in low−cost AC−DC adapters, auxiliary supplies etc. Due to its high−performance SMARTMOS High−V oltage technology, the NCP1203 incorporates all the necessary components normally needed in UC384X based supplies: timing components, feedback devices, low−pass filter and startup device. This later point emphasizes the fact that ON Semiconductor’s NCP1203 does not need an external startup resistance but supplies the startup current directly from the high−voltage rail. On the other hand, more and more applications are requiring low no−load standby power, e.g. for AC−DC adapters, VCRs etc. UC384X series have a lot of difficulty to reduce the switching losses at low power levels. NCP1203 elegantly solves this problem byskipping unwanted switching cycles at a user−adjustable power level. By ensuring that skip cycles take place at low peak current, the device ensures quiet, noise free operation.Finally, an auto−recovery output short−circuit protection (OCP) prevents from any lethal thermal runaway in overload conditions.Startup SequenceWhen the power supply is first powered from the mains outlet, the internal current source (typically 6.0 mA) is biased and charges up the V CC capacitor. When the voltage on this V CC capacitor reaches the V CC(on) level (typically 12.8 V), the current source turns off and no longer wastes any power. At this time, the V CC capacitor only supplies the controller and the auxiliary supply is supposed to take over before V CC collapses below V CC(min). Figure 13 shows the internal arrangement of this structure:Figure 13. The Current Source Brings V CC Above 12.8 V and then Turns OffAux12.8 V/4.9 VOnce the power supply has started, the V CC shall be constrained below 16 V , which is the maximum rating on pin 6. Figure 14 portrays a typical startup sequence with a V CC regulated at 12.5 V:Figure 14. A Typical Startup Sequence forthe NCP1203t, TIME (sec)13.512.511.510.59.5Current−Mode OperationAs the UC384X series, the NCP1203 features a well−known current mode control architecture which provides superior input audio−susceptibility compared to traditional voltage−mode controllers. Primary current pulse−by−pulse checking together with a fast over current comparator offers greater security in the event of a difficult fault condition, e.g. a saturating transformer.Adjustable Skip Cycle LevelBy offering the ability to tailor the level at which the skip cycle takes place, the designer can make sure that the skip operation only occurs at low peak current. This point guarantees a noise−free operation with cheap transformers. Skip cycle offers a proven mean to reduce the standby power in no or light loads situations.Wide Switching−Frequency OfferFour different options are available: 40 kHz − 65 kHz –100 kHz. Depending on the application, the designer can pick up the right device to help reducing magnetics or improve the EMI signature before reaching the 150 kHz starting point.Overcurrent Protection (OCP)When the auxiliary winding collapses below UVLOlow, the controller stops switching and reduces its consumption. It stays in this mode until Vcc reaches 4.9 V typical, where the startup source is reactivated and a new startup sequence is attempted. The power supply is thus operated in burst mode and avoids any lethal thermal runaway. When the default goes way, the power supply automatically resumes operation.Wide Duty−Cycle OperationWide mains operation requires a large duty−cycle excursion. The NCP1203 can go up to 80% typically.Low Standby PowerIf SMPS naturally exhibit a good efficiency at nominal load, they begin to be less efficient when the output power demand diminishes. By skipping un−needed switching cycles, the NCP1203 drastically reduces the power wasted during light load conditions. In no−load conditions, the NCP1203 allows the total standby power to easily reach next International Energy Agency (IEA) recommendations.No Acoustic Noise while OperatingInstead of skipping cycles at high peak currents, the NCP1203 waits until the peak current demand falls below a user−adjustable 1/3rd of the maximum limit. As a result, cycle skipping can take place without having a singing transformer … You can thus select cheap magnetic components free of noise problems.External MOSFET ConnectionBy leaving the external MOSFET external to the IC, you can select avalanche proof devices which, in certain cases (e.g. low output powers), let you work without an active clamping network. Also, by controlling the MOSFET gate signal flow, you have an option to slow down the device commutation, therefore reducing the amount of ElectroMagnetic Interference (EMI).SPICE ModelA dedicated model to run transient cycle−by−cycle simulations is available but also an averaged version to help you closing the loop. Ready−to−use templates can be downloaded in OrCAD’s Pspice and INTUSOFT’s from ON Semiconductor web site, NCP1203 related section. Overload OperationIn applications where the output current is purposely not controlled (e.g. wall adapters delivering raw DC level), it is interesting to implement a true short−circuit protection. A short−circuit actually forces the output voltage to be at a low level, preventing a bias current to circulate in the optocoupler LED. As a result, the auxiliary voltage also decreases because it also operates in Flyback and thus duplicates the output voltage, providing the leakage inductance between windings is kept low. To account for this situation and properly protect the power supply, NCP1203 hosts a dedicated overload detection circuitry. Once activated, this circuitry imposes to deliver pulses in a burst manner with a low duty−cycle. The system auto−recovers when the fault condition disappears.During the startup phase, the peak current is pushed to the maximum until the output voltage reaches its target and the feedback loop takes over. The auxiliary voltage takes place after a few switching cycles and self−supplies the IC. In presence of a short circuit on the output, the auxiliary voltage will go down until it crosses the undervoltage lockout level of typically 7.8 V. When this happens, NCP1203 immediately stops the switching pulses and unbias all unnecessary logical blocks. The overall consumption drops, while keeping the gate grounded, and the V CC slowly falls down. As soon as V CC reaches typically 4.8 V, the startup source turns−on again and a new startup sequence occurs, bringing V CC toward 12.8 V as an attempt to restart. If the default has gone, then the power supply normally restarts. If not, a new protective burst is initiated, shielding the SMPS from any runaway. Figure 15, on the following page, portrays the typical operating signals in short circuit.Figure 15. Typical Waveforms in Short Circuit Conditions7.8 V12.8 V4.9 VV CCDRIVING PULSESCalculating the V CC CapacitorThe V CC capacitor can be calculated knowing the IC consumption as soon as V CC reaches 12.8 V . Suppose that a NCP1203P60 is used and drives a MOSFET with a 30 nC total gate charge (Qg). The total average current is thus made of ICC1 (700 m A) plus the driver current, Fsw x Qg or 1.8 mA. The total current is therefore 2.5 mA. The D V available to fully startup the circuit (e.g. never reach the 7.8 V UVLO during power on) is 12.8–7.8 = 5 V . We have a capacitor who then needs to supply the NCP1203 with 2.5 mA during a given time until the auxiliary supply takes over. Suppose that this time was measured at around 15 ms.CV CC is calculated using the equation C +D t ·i D VorC w 7.5m F . Select a 22 m F/16 V and this will fit.Skipping Cycle ModeThe NCP1203 automatically skips switching cycles when the output power demand drops below a given level. This is accomplished by monitoring the FB pin. In normal operation, pin 2 imposes a peak current accordingly to the load value. If the load demand decreases, the internal loop asks for less peak current. When this setpoint reaches a determined level (Vpin 1), the IC prevents the current from decreasing further down and starts to blank the output pulses: the IC enters the so−called skip cycle mode, also named controlled burst operation. The power transfer now depends upon the width of the pulse bunches (Figure 17).Suppose we have the following component values:Lp, primary inductance = 350 m H Fsw , switching frequency = 61 kHz Ip skip = 600 mA (or 333 mV/Rsense)The theoretical power transfer is therefore:12·Lp ·Ip 2·Fsw +3.8W If this IC enters skip cycle mode with a bunch length of 10 ms over a recurrent period of 100 ms, then the total power transfer is: 3.8.0.1+380mW .To better understand how this skip cycle mode takes place,a look at the operation mode versus the FB level immediately gives the necessary insight:Figure 16.When FB is above the skip cycle threshold (1.0 V by default), the peak current cannot exceed 1.0 V/Rsense.When the IC enters the skip cycle mode, the peak current cannot go below Vpin1/3.3/Rsense. The user still has the flexibility to alter this 1.0 V by either shunting pin 1 to ground through a resistor or raising it through a resistor up to the desired level. Grounding pin 1 permanently invalidates the skip cycle operation. However, given the extremely low standby power the controller can reach, the PWM in no−load conditions can quickly enter the minimum t on and still transfer too much power. An instability can take place. We recommend in that case to leave a little bit of skip level to always allow 0% duty cycle.Power P1Power P2Power P3Figure 17. Output Pulses at Various Power Levels (X = 5.0 m s/div) P1 t P2 t P3Figure 18. The Skip Cycle Takes Place at Low Peak Currents which Guaranties Noise−Free Operation315.40882.70 1.450 M 2.017 M 2.585 M300 M200 M100 MWe recommend a pin 1 operation between 400 mV and 1.3 V that will fix the skip peak current level between 120 mV/Rsense and 390 mV/Rsense.Non−Latching ShutdownIn some cases, it might be desirable to shut off the part temporarily and authorize its restart once the default hasdisappeared. This option can easily be accomplished through a single NPN bipolar transistor wired between FB and ground. By pulling FB below the Adj pin 1 level, the output pulses are disabled as long as FB is pulled below pin 1. As soon as FB is relaxed, the IC resumes its operation.Figure 19 depicts the application example.Figure 19. Another Way of Shutting Down the IC without a Definitive Latch−Off StateFull Latching ShutdownOther applications require a full latching shutdown, e.g.when an abnormal situation is detected (overtemperature or overvoltage). This feature can easily be implemented through two external transistors wired as a discrete SCR.When the V CC level exceeds the zener breakdown voltage,the NPN biases the PNP and fires the equivalent SCR,permanently bringing down the FB pin. The switching pulses are disabled until the user unplugs the power supply.Figure 20. Two Bipolars Ensure a Total Latch−Off of the SMPS in Presence of an OVPLAuxRhold 0.1 m Rhold ensures that the SCR stays on when fired. The bias current flowing through Rhold should be small enough to let the V CC ramp up (12.8 V) and down (4.9 V) when the SCR is fired. The NPN base can also receive a signal from a temperature sensor. Typical bipolars can be MMBT2222and MMBT2907 for the discrete latch. The MMBT3946features two bipolars NPN+PNP in the same package and could also be used.Protecting the Controller Against Negative SpikesAs with any controller built upon a CMOS technology, it is the designer’s duty to avoid the presence of negative spikes on sensitive pins. Negative signals have the bad habit to forward bias the controller substrate and induce erratic behaviors. Sometimes, the injection can be so strong that internal parasitic SCRs are triggered, engendering irremediable damages to the IC if they are a low impedance path is offered between V CC and GND. If the current sensepin is often the seat of such spurious signals, the high−voltage pin can also be the source of problems in certain circumstances. During the turn−off sequence, e.g.when the user un−plugs the power supply, the controller is still fed by its V CC capacitor and keeps activating the MOSFET ON and OFF with a peak current limited by Rsense. Unfortunately, if the quality coefficient Q of the resonating network formed by Lp and Cbulk is low (e.g. the MOSFET Rdson + Rsense are small), conditions are met to make the circuit resonate and thus negatively bias the controller. Since we are talking about ms pulses, the amount of injected charge (Q = I x t) immediately latches the controller which brutally discharges its V CC capacitor. If this V CC capacitor is of sufficient value, its stored energy damages the controller. Figure 21 depicts a typical negative shot occurring on the HV pin where the brutal V CC discharge testifies for latchup.Figure 21. A negative spike takes place on the Bulk capacitor at the switch−off sequenceSimple and inexpensive cures exist to prevent from internal parasitic SCR activation. One of them consists in inserting a resistor in series with the high−voltage pin to keep the negative current to the lowest when the bulk becomes negative (Figure 22). Please note that the negative spike is clamped to –2 x Vf due to the diode bridge. Also, the power dissipation of this resistor is extremely small since it only heats up during the startup sequence.Another option (Figure 23) consists in wiring a diode from V CC to the bulk capacitor to force V CC to reach UVLOlow sooner and thus stops the switching activity before the bulk capacitor gets deeply discharged. For security reasons, two diodes can be connected in series.Figure 22. A simple resistor in series avoids anylatchup in the controllerCV CCD31N4007CV CCRbulk > 4.7 kFigure 23. or a diode forces V CC to reachUVLOlow sooner†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specifications Brochure, BRD8011/D.D1, D2 SUFFIX CASE 751−07ISSUE AC*For additional information on our Pb−Free strategy and solderingdetails, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.SOLDERING FOOTPRINT*NOTES:1.DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982.2.CONTROLLING DIMENSION: MILLIMETER.3.DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION.4.MAXIMUM MOLD PROTRUSION 0.15 (0.006)PER SIDE.5.DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBARPROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION.6.751−01 THRU 751−06 ARE OBSOLETE. NEW STANDARD IS 751−07.DIM A MIN MAX MIN MAX INCHES4.805.000.1890.197MILLIMETERS B 3.80 4.000.1500.157C 1.35 1.750.0530.069D 0.330.510.0130.020G 1.27 BSC 0.050 BSC H 0.100.250.0040.010J 0.190.250.0070.010K 0.40 1.270.0160.050M 0 8 0 8 N 0.250.500.0100.020S5.806.200.2280.244YM0.25 (0.010)Z SXS____ǒmm inchesǓSCALE 6:1N SUFFIX CASE 626−05ISSUE LNOTES:1.DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL.2.PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS).3.DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982.DIM MIN MAX MIN MAX INCHESMILLIMETERS A 9.4010.160.3700.400B 6.10 6.600.2400.260C 3.94 4.450.1550.175D 0.380.510.0150.020F 1.02 1.780.0400.070G 2.54 BSC 0.100 BSC H 0.76 1.270.0300.050J 0.200.300.0080.012K 2.92 3.430.1150.135L 7.62 BSC 0.300 BSC M −−−10 −−−10 N0.76 1.010.0300.040__ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates,and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.PUBLICATION ORDERING INFORMATIONThe product described herein (NCP1203), may be covered by the following U.S. patents: 6,271,735, 6,362,067, 6,385,060, 6,429,709, 6,587,357. There may be other patents pending.SMARTMOS is a trademark of Motorola, Inc.。
单端PWM控制器NCP1205及其应用
单端PWM控制器NCP1205及其应用ＮＣＰ１２０５是安森美公司采用先进技术生产的一种单端脉冲宽度调制控制器。
该控制器可保证在任何负载／线路条件下的完全继续传导模式ＤＣＭ和准谐振ＱＲ操作，同时，该器件还组合了一个真正的电流模式控制调制器和一个退磁检测器。
文中介绍了ＮＣＰ１２０５ＰＷＭ控制芯片的基本构造、工作原理和主要特点，给出了它的典型应用电路。
１概述ＮＣＰ１２０５是安森美公司生产的一种先进的单端ＰＷＭ控制器。
其应用领域主要包括：较大功率笔记本电脑用ＡＤ／ＤＣ适配器、脱机电池充电器和ＤＶＤ、ＣＤ唱机、ＴＶＳ、机顶盒（ＳＴＢ）等系统的开关电流（ＳＭＰＳ）及ＵＳＢ中的辅助电源等。
ＮＣＰ１２０５以准谐振（ＱＲ）操作和频率软折弯为主要特征。
ＱＲ操作也是临界传导操作，可以保证功率ＭＯＳＦＥＴ在最小的漏－漏极电压上完成开关（亦称作谷值开关）。
ＮＣＰ１２０５采用平滑频率减小技术，是低功率ＳＭＰＳ集成管理方面的一个重要创新。
由于ＮＣＰ１２０５有变频模式（ＶＦＭ），因此当输出功率要求减小时，可以在不变的峰值电流上降低它的工作频率。
ＮＣＰ１２０５通过谷值开关与软频率折弯特性相结合的方法可保证实现最低的开关损耗，同时可在无载条件操作时从电网吸取最低的功率，此外还可以保证具有最小的ＥＭＩ。
２引脚功能和构造特点２.１引脚功能ＮＣＰ１２０５采用８脚ＰＤＩＰ（ＮＣＰ１２０５）、１４脚ＰＤＩＰ（ＮＣＰ１２０５ＳＰ２）和１６脚ＳＯ（ＮＣＰ１２０５ＤＲ２）３种封装形式，表１给出了１４脚ＰＤＩＰ封装的引脚功能说明。
表1NCP1205P2的引脚功能脚号引脚名称功能描述1HV连接已整流的高压（HV）总线，便在IC启动时对外部大容量电容提供充电通路2、7、8、9、14NC未连接3Demag零初级电流检测，自由振荡下操作可保证主开关重新启动4FB反应信号输入，用于控制PWM5Ct与地之间连接一只电容器可设定最小/最大工作频率6OVP过电压保护输入，门限电平是2.8V10GND接地11Isense电流检测输入12DRVMOS栅极驱动输出13Vcc 正电流电压施加端２.２构造特点ＮＣＰ１２０５虽然采用三种封装形式，但片内构造和电路组成基本一样。
1203 WEIGHT TRANSMITTER操作手册说明书
Rinstrum 1203 reference Manual1203WEIGHTTRANSMITTERReferenceManualFor use with SoftwareVersions 1.x1203-600 Rev 1.41. INTRODUCTION (4)1.1. Document Conventions (4)2. SPECIFICATIONS (5)3. INSTALLATION (6)3.1. Introduction (6)3.2. Power Supply (6)3.3. Load Cell Signals and Scale Build (6)3.4. Cable Shield Connection and Earthing (6)3.5. Load Cell Connection (7)Connection (7)3.5.1. 6-WireConnections (8)3.5.2. 4-Wire3.6. Intrinsic Safety (9)3.7. Serial Communication Ports (9)3.7.1. Serial 1: RS-232 Port (10)3.7.2. Serial 2: RS-485 Port (10)Networking (11)3.7.3. Multi-DropConnection (11)3.7.4. RS-232Connection (12)3.7.5. RS-4853.8. Input / Output: Setpoints (13)3.9. Input / Output: Inputs (14)3.10. Analog Output (15)3.11. LEDs (15)3.12. 1203 Viewer Software (15)4. CONTROLS (16)SETUP (17)5. DIGITAL5.1. Introduction (17)5.2. Basic Weighing Terminology (17)5.3. Direct mV/V Operation (18)5.4. Filtering Techniques (18)Filter (18)5.4.1. FIRAveraging (18)5.4.2. Digital6. CALIBRATION (19)6.1. Introduction (19)6.2. Digital Calibration with Test Weights (19)6.2.1. Digital Zero Calibration Routine (19)6.2.2. Digital Span Calibration Routine (19)6.3. Digital Direct mV/V Calibration (20)6.3.1. Digital Zero Calibration Routine (20)6.3.2. Digital Span Calibration Routine (20)6.4. Analog Output Calibration (20)6.4.1. Analog Calibration Routine (20)OUTPUTS (21)7. SERIAL7.1. Introduction (21)7.2. Automatic Weight Output (21)7.3. Networking the 1203 (21)7.3.1. RS-485Resistors (21)TerminationFUNCTIONS (22)8. EXTENDED8.1. Setpoints (22)8.1.1. Introduction (22)8.1.2. StatusIndication (22)8.1.3. Connection (22)8.1.4. Operation (22)8.1.5. Example 1: Control Level of Product in 2000kg Tank (23)8.1.6. Example 2: Control Weighing of Product Out of Silo into 100kg Drums (23)8.2. Remote Input (23)9. OPTIONS (24)9.1. Display/Keys (24)9.1.1. Installation (24)9.1.2. Setup and Calibration (24)10. COMMANDS (25)10.1. Overview (25)10.1.1. Commands and Queries (25)10.1.2. Responses (25)10.1.3. Parameters (25)10.1.4. Termination (25)10.2. Command Details (26)10.2.1. ACL: Set Automatic Temperature Calibration On/Off (26)10.2.2. ADR: Set Address (27)10.2.3. ANL: Set Analog Output (28)10.2.4. ANM: Set Analog Output Maximum and Minimum (29)10.2.5. ASF: Set Filtering (30)10.2.6. BDR: Set Baud Rate (31)10.2.7. COF: Set Output Format (32)10.2.8. ESR: Query Error Status (35)10.2.9. FCN: Execute A Function (36)10.2.10. HYS: Set Hysteresis (37)10.2.11. IAD: Set Scale Build (38)10.2.12. IDN: Set Identification (39)10.2.13. LDW: Calibrate Zero Dead Weight (40)10.2.14. LIV: Set Limit Value (41)10.2.15. LWT: Calibrate Span (42)10.2.16. MSV?: Query Measured Weight Value (43)10.2.17. RBT: Remote Button Settings (44)10.2.18. RES: Reset (46)10.2.19. SER: Set Serial Communications Settings (47)10.2.20. STP: Stop Continuous Transfer (48)10.2.21. Sxx: Select Unit (49)10.2.22. TAR: Tare (50)10.2.23. TDD: Load/Save Setup (51)11. APPENDIX (52)11.1. Glossary (52)11.2. List of Figures and Tables (52)12. INDEX (53)This is a “Table of Contents preview” for quality assuranceThe full manual can be found at /estore/catalog/ We also offer free downloads, a free keyboard layout designer, cable diagrams, free help andsupport. : the biggest supplier of cash register and scale manuals on the net。
NCP1230 组成的适配器电源
NCP1230 组成的适配器电源综述NCP1230执行一个标准的电流型反激变换器控制结构，它是用在元件少，低成本适配器的最佳候选IC，NCP1230综合了低备用电流及故障管理功能。
并给出在待机时禁止PFC的功能，这就大幅降低了带PFC的ADAPTOR的空载功耗，本文用一个90W样板来介绍NCP1230的上述各项功能。
NCP1230有一个PFC的VCC输出端，它用来给PFC的控制器提供电源，PFC的VCC端在输出电压高出，待机时被禁止，故障时，PFC的VCC端关闭。
禁止PFC控制器工作，减小了PFC半导体元件的应力。
此外，为挑战空载功耗。
NCP1230还提供一个内部锁存功能。
它可以用于过压保护，用的方法是将CS端电压推上至3V。
特点：●电流型控制●低压功耗启动●在全电压范围内工作●直控PFC控制器●极低待机功耗●过压保护设计规范：该样板分作两级适配电源，第一级工作在全范围输入时关断。
它使用MC33260的临界导通型控制。
即工作在跟随型，输出电压在此时（85VAC）为200V。
随输入电压增加到230VAC。
输出将升至400VDC。
第二级为NCP1230的反激变换级。
第二级输出为19VDC。
并给出90W供电能力。
它为整个自保持包括编置电源，此时变压器辅助绕组工作关断。
样板规范需求符号最小最大输入电压Vin AC 85V 265V频率 F Hz 47 63输出电压Vout V 18.6V 19.38V输出电流Iout A -- 4.74A输出功率Pout W -- 90W效率η80 --空载功率230V mW -- 150mW短路功耗230V mW -- 100mW轻载功耗0.5Wload mW -- 800mWPFCMC33260设计为跟随型升压工作模式，它设计为提供116W输出功率的模式。
I pk = 8 0.5 Pinmax/VacI pk = 8 0.5 *116 / 85 = 3.86AMC33260是一个临界导通型控制器，其工作频率是升压电感和定时电容的函数，在本应用中最低工作频率为30KHz 。